CN104932594B - Ripple controlled switching regulator and method for ripple controlled switching regulator - Google Patents

Abstract

The invention discloses a ripple control switching type voltage stabilizer which comprises a switch, an inductor, a capacitor, an output voltage processing unit and a control unit. The switch is used for selectively outputting a first reference voltage or a second reference voltage as an output voltage according to a control signal. The inductor is coupled to the switcher and generates an inductor output voltage according to the output voltage. The capacitor is coupled to the inductor. The output voltage processing unit is used for outputting a processed inductor output voltage according to the output voltage and the inductor output voltage. The control unit is used for outputting the control signal at least according to the processed inductor output voltage.

Description

Ripple controlled switching regulator and method for ripple controlled switching regulator

technical field

The embodiments disclosed in the present invention relate to a switching regulator, especially a switching regulator with ripple-based control and a related ripple-based switching regulator method. .

Background technique

The feature of the ripple control switching regulator can instantly feed back the output voltage across the filter capacitor and judge accordingly. Whether to charge or discharge the inductor, when the output voltage fed back is less than the preset reference voltage, it will be determined by turning on the transistor switch of the upper bridge and turning off the transistor switch of the lower bridge for a fixed power supply time (on time). The action of charging the inductor increases the output voltage of the switching regulator. When the power supply time is over and the output voltage fed back is greater than the preset reference voltage, the inductor will be discharged by turning off the transistor switch of the upper bridge and turning on the transistor switch of the lower bridge, reducing the switching voltage regulator. The output voltage.

However, due to the parasitic inductance of the filter capacitor, when the switching regulator is charging, the parasitic inductance of the filter capacitor will form a positive cross-voltage; conversely, when the switching regulator is discharging, the parasitic inductance of the filter capacitor will form Negative voltage across. Therefore, when the power supply time is over, the positive cross-voltage of the parasitic inductance of the filter capacitor will instantly convert to a negative cross-voltage, which will pull down the overall output voltage of the filter capacitor, and may be lower than the preset reference voltage immediately, resulting in continuous triggering Two power-on times (ie, double pulses) lead to putting too much energy into the inductor and exacerbating the subharmonic oscillation of the output voltage. Therefore, in the prior art, the inductor current is usually directly measured instead of the voltage of the filter capacitor to avoid the influence of the parasitic inductance. However, the method of directly measuring the inductor current is expensive and has a large measurement error. In view of this, there is an urgent need in the art for a novel ripple control switching regulator to improve the above problems.

Contents of the invention

One of the objectives of the present invention is to provide a ripple control switching regulator capable of correcting the parasitic inductance effect of the filter capacitor and a related method to improve the problem of sub-harmonic oscillation.

According to an exemplary embodiment of the present invention, a ripple control switching regulator is provided, including a switcher, an inductor, a capacitor, an output voltage processing unit, and a control unit. Wherein the switch is used to selectively output a first reference voltage or a second reference voltage as an output voltage according to a control signal. The inductor is coupled to the switch, and generates an inductor output voltage according to the output voltage. The capacitor is coupled to the inductor. The output voltage processing unit is used to output a processed inductor output voltage according to the output voltage and the inductor output voltage. The control unit is used for outputting the control signal at least according to the processed inductor output voltage.

According to another exemplary embodiment of the present invention, a ripple-based control switching regulator method is proposed for controlling a ripple-based switching regulator, wherein the ripple-based control The switching regulator includes a switch, an inductor coupled to the switch, and a capacitor coupled to the inductor, the ripple control switching regulator method includes: using the switch to select according to a control signal Outputting a first reference voltage or a second reference voltage as an output voltage; using the inductor to generate an inductor output voltage according to the output voltage; outputting a processed inductor according to the output voltage and the inductor output voltage an output voltage; and using the control unit to output the control signal at least according to the processed inductor output voltage.

The embodiment disclosed in this specification utilizes the correction of parasitic inductance effect to avoid double pulse. At the same time, compared with the practice of directly measuring the inductor current in the traditional design, the practice of correcting the parasitic inductance effect in this specification has lower cost and less error. Minor pluses.

Description of drawings

FIG. 1 is a schematic diagram of an exemplary embodiment of a ripple control switching regulator of the present invention.

FIG. 2 is a waveform diagram of the voltage and current of each element in the filter capacitor.

FIG. 3 is a circuit diagram of an exemplary embodiment of a parasitic inductance correction unit of the present invention.

FIG. 4 is a circuit diagram of an exemplary embodiment of a specific voltage gain adjustment unit of the present invention.

FIG. 5 is a flow chart of an embodiment of a ripple control switching voltage stabilization method according to the present invention.

Wherein, the reference signs are explained as follows:

100 Ripple Controlled Switching Regulator

102 switcher

104 inductance

106 filter capacitor

108 output voltage processing unit

110 control unit

112 Specific voltage gain adjustment unit

1022, 1024 metal oxide semiconductor

1082 double pulse detection unit

1084 Voltage Correction Unit

10842 Parasitic Inductance Correction Unit

10844 Differentiator

1102 Comparator

1104 Constant on-time unit

1106 Non-overlapping processing units

108422, 1122 Operational Amplifiers

108424 Gain adjustment circuit

108426, 1124 voltage divider circuit

Steps from S502 to S514

detailed description

Please refer to FIG. 1 , which is a schematic diagram of an exemplary embodiment of a ripple-based control switching regulator (switching regulator) 100 of the present invention. The ripple control switching regulator 100 is used to provide stable voltage under different load conditions, and its main functional blocks and technical features of this embodiment will be described in detail as follows. Firstly, a switcher 102 is used to control a P-type MOS 1022 and an N-type MOS 1024 connected in series according to an upper-bridge control signal S _up and a lower-bridge control signal S _down to switch a supply voltage VCC or It is a ground voltage GND output as an output voltage V _s (please note that the present invention is not limited to N-type metal oxide semiconductors and P-type metal oxide semiconductors, in fact any switch that can provide the same function belongs to the present invention scope). Specifically, when the upper-bridge control signal S _up controls the P-type MOS 1022 in the switch 102 to conduct, and the lower-bridge control signal S _down controls the N-type MOS 1024 in the switch 102 to be non-conductive, The supply voltage VCC will charge an inductor 104 coupled to the switch 102; otherwise, when the upper bridge control signal S _up controls the P-type metal oxide semiconductor 1022 in the switch 102 to be non-conductive, and the lower bridge control signal S _down controls the action that the ground voltage GND discharges the inductor 104 coupled to the switch 102 when the NMOS 1024 in the switch 102 is turned on. Generally speaking, the ripple control switching regulator 100 will control the switcher 102 to charge the inductor 104 for a fixed power supply time (on time) when it determines that an inductor output voltage V _ripple of the inductor 104 is less than a specific voltage V _ref )T _ontime , when the power supply time T _ontime ends, the charging will stop, and continue to monitor whether the inductor output voltage V _ripple is lower than the specific voltage V _ref , once the inductor output voltage V _ripple is lower than the specific voltage V _ref , it will control the switch 102 again to the inductor 104 charging and supplying power for a time T _ontime .

The ripple control switching regulator 100 uses a filter capacitor 106 across the inductor output voltage V _ripple and the ground voltage GND. The filter capacitor 106 has parasitic resistance and parasitic inductance effects, so a capacitor C and an inductor L are used. and a resistor R to represent the equivalent filter capacitor 106 . Please refer to FIG. 2 at the same time. FIG. 2 is a waveform diagram of the voltage and current of each element in the filter capacitor 106 . When the switch 102 charges the inductance 104 (that is, a time t1 to a time t2, wherein the interval from the time t1 to the time t2 is the power supply time T _ontime ; and a time t3 to a time t4, wherein the time t3 to the time t4 The interval is the power supply time T _ontime ), there will be a current I _ac flowing through the filter capacitor 106, and the slope of the current I _ac is a positive value, as can be obtained from Figure 2, the differential of the slope of a voltage V _c across the capacitor C It will also be a positive value, the slope of the voltage V _ESR across the resistor R is also positive, and the voltage V _ESL across the inductor L will maintain a fixed positive value. Finally, add the cross voltage V _c , the cross voltage V _ESR and the cross voltage V _ESL to obtain the inductor output voltage V _ripple . Conversely, when the switch 102 discharges the inductor 104 (that is, from a time t2 to a time t3; and from a time t4 to a time t5), the slope of the current I _ac is a negative value, which can be obtained from FIG. 2 , The differential of the slope of the voltage V _c across the capacitor C will also be negative, the slope of the voltage V _ESR across the resistor R will also be negative, and the voltage V _ESL across the inductor L will maintain a constant negative value.

Therefore, whenever the upper bridge control signal S _up controls the P-type MOS 1022 in the switcher 102 to conduct and maintain the power supply time T _ontime , then the N-type MOS 1024 in the switcher 102 is turned on, and the inductor output The voltage V _ripple will decrease instantaneously due to the instantaneous decrease of the cross-voltage V _ESL , so that the inductor output voltage V _ripple is lower than the specific voltage V _ref , and immediately triggers the upper bridge control signal S _up again to control the oxidation of the P-type metal in the switch 102 The semiconductor 1022 is turned on and maintains the power supply time T _ontime , that is, a double pulse (not shown in the figure), which causes excessive charging of the inductor 104 . In view of this, the feature of the present invention is that an output voltage processing unit 108 can be used to correct the inductor output voltage V _ripple , that is, the part of the parasitic inductance L (cross-voltage V _ESL ) in the inductor output voltage V _ripple is eliminated to avoid double Adverse effects brought about by the pulse.

The output voltage processing unit 108 is used to output a processed inductor output voltage V _d according to the output voltage V _s and the inductor output voltage V _ripple . The output voltage processing unit 108 includes a double pulse detection unit 1082 and a voltage correction unit 1084 . The double pulse detection unit 1082 is used to detect whether the output voltage V _s contains double pulses and generate a detection result S _det , for example, when the time interval between two pulses in the output voltage V _s is less than a specific time, the output voltage V _s is judged Including double pulses, the judging method of the double pulse detection unit 1082 can have many design changes, but as long as they are based on the same basis or can produce similar effects, they all belong to the scope of the present invention. In addition, the voltage correction unit 1084 is used to generate the processed inductor output voltage according to the detection result S _det , the output voltage V _s and the inductor output voltage V _ripple . The voltage correction unit 1084 includes a parasitic inductance correction unit 10842 and a differentiator 10844 . The parasitic inductance correction unit 10842 is used to generate a corrected output voltage V _cal without the parasitic inductance L across the voltage V _ESL according to the detection result S _det , the output voltage V _s and the inductor output voltage V _ripple . Please refer to Figure 2 again, because circuit designers generally want to use information such as current I _ac to compare with a specific voltage V _ref , but the corrected output obtained by canceling the inductor L’s cross voltage V _ESL from the inductor output voltage V _ripple The voltage V _cal is mainly the information of the cross-voltage V _c of the capacitor C (the cross-voltage V _ESR of the resistor R is small and negligible), and the cross-voltage V _c needs to be differentiated to form a synchronous change with the current I _ac , that is, After the corrected output voltage V _cal is obtained, the differentiator 10844 needs to be used to differentiate the corrected output voltage V _cal to generate the processed inductor output voltage V _d .

Regarding the parasitic inductance correction unit 10842, please refer to FIG. 3, which is a circuit diagram of an exemplary embodiment of the parasitic inductance correction unit 10842 of the present invention. The parasitic inductance correction unit 10842 includes an operational amplifier 108422 , a gain adjustment circuit 108424 and a voltage dividing circuit 108426 . The operational amplifier 108422 includes a first input terminal, a second input terminal and an output terminal, wherein the first input terminal is used to receive the inductor output voltage V _ripple , the output terminal outputs the corrected output voltage V _cal , and the gain adjustment circuit 108424 has a variable gain value g, which is used to perform a gain process on the output voltage V _s and generate a gain output voltage V _g ,

V _g =V _s *g (1)

The variable gain value g can be adjusted according to the detection result S _det . For example, when the ripple control switching regulator 100 is powered on, when the detection result S _det shows that the output voltage V _s contains double pulses, the gain value g of the gain adjustment circuit 108424 increases from an initial gain until the detection result S det The result S _det shows that the output voltage V _s does not contain double pulses. When the next test result S _det shows that the output voltage V _s contains double pulses, the gain value g of the gain adjustment circuit 108424 can be increased from the current gain value. The adjustment method of the gain adjustment circuit 108424 can have many design changes, but as long as it is based on The same basis or the ability to produce similar effects all belong to the scope of the present invention. It should be noted that since the waveform of the output voltage V _s is basically consistent with the voltage V _ESL across the inductor L, the output voltage V _s is used to eliminate the part of the voltage V _ESL across the inductor output voltage V _ripple , so Equation (1) can be rewritten as follows:

V _g =V _ESL *x (2)

One of the ratio x is the ratio of the gain output voltage V _g to the voltage across the inductor L V _ESL .

The voltage dividing circuit 108426 includes a first resistor R1 and a second resistor R2 connected in series, wherein the first resistor R1 is coupled between the output terminal of the operational amplifier 108422 and the second input terminal of the operational amplifier 108422, the second Two resistors R2 are coupled between the second input terminal of the operational amplifier 108422 and the gain adjustment circuit 108424 to form a negative feedback circuit, and the voltage of the positive second input terminal of the operational amplifier 108422 remains the same, therefore, by the following equation (3) can get:

${\mathrm{<span\; class="notranslate">\; V</span>}}_{\mathrm{<span\; class="notranslate">\; cal</span>}}<span\; class="notranslate">\; =</span><span\; class="notranslate">\; (</span>\frac{\mathrm{<span\; class="notranslate">\; R</span>}\mathrm{<span\; class="notranslate">\; 1</span>}<span\; class="notranslate">\; +</span>\mathrm{<span\; class="notranslate">\; R</span>}\mathrm{<span\; class="notranslate">\; 2</span>}}{\mathrm{<span\; class="notranslate">\; R</span>}\mathrm{<span\; class="notranslate">\; 2</span>}}<span\; class="notranslate">\; )</span><span\; class="notranslate">\; (</span>{\mathrm{<span\; class="notranslate">\; V</span>}}_{\mathrm{<span\; class="notranslate">\; ESR</span>}}<span\; class="notranslate">\; +</span>{\mathrm{<span\; class="notranslate">\; V</span>}}_{\mathrm{<span\; class="notranslate">\; c</span>}}<span\; class="notranslate">\; )</span><span\; class="notranslate">\; +</span>{\mathrm{<span\; class="notranslate">\; V</span>}}_{\mathrm{<span\; class="notranslate">\; ESR</span>}}<span\; class="notranslate">\; (</span>\frac{\mathrm{<span\; class="notranslate">\; R</span>}\mathrm{<span\; class="notranslate">\; 1</span>}<span\; class="notranslate">\; +</span>\mathrm{<span\; class="notranslate">\; R</span>}\mathrm{<span\; class="notranslate">\; 2</span>}}{\mathrm{<span\; class="notranslate">\; R</span>}\mathrm{<span\; class="notranslate">\; 2</span>}}<span\; class="notranslate">\; -</span>\frac{\mathrm{<span\; class="notranslate">\; R</span>}\mathrm{<span\; class="notranslate">\; 1</span>}<span\; class="notranslate">\; *</span>\mathrm{<span\; class="notranslate">\; x</span>}}{\mathrm{<span\; class="notranslate">\; R</span>}\mathrm{<span\; class="notranslate">\; 2</span>}}<span\; class="notranslate">\; )</span><span\; class="notranslate">\; -</span><span\; class="notranslate">\; -</span><span\; class="notranslate">\; -</span><span\; class="notranslate">\; (</span>\mathrm{<span\; class="notranslate">\; 3</span>}<span\; class="notranslate">\; )</span>$

In this way, when

$\mathrm{<span\; class="notranslate">\; x</span>}<span\; class="notranslate">\; =</span>\frac{\mathrm{<span\; class="notranslate">\; R</span>}\mathrm{<span\; class="notranslate">\; 1</span>}<span\; class="notranslate">\; +</span>\mathrm{<span\; class="notranslate">\; R</span>}\mathrm{<span\; class="notranslate">\; 2</span>}}{\mathrm{<span\; class="notranslate">\; R</span>}\mathrm{<span\; class="notranslate">\; 1</span>}}<span\; class="notranslate">\; -</span><span\; class="notranslate">\; -</span><span\; class="notranslate">\; -</span><span\; class="notranslate">\; (</span>\mathrm{<span\; class="notranslate">\; 4</span>}<span\; class="notranslate">\; )</span>$

, the part of the voltage V _ESL across the inductor L in the corrected output voltage V _cal can be completely eliminated, that is

${\mathrm{<span\; class="notranslate">\; V</span>}}_{\mathrm{<span\; class="notranslate">\; cal</span>}}<span\; class="notranslate">\; =</span><span\; class="notranslate">\; (</span>\frac{\mathrm{<span\; class="notranslate">\; R</span>}\mathrm{<span\; class="notranslate">\; 1</span>}<span\; class="notranslate">\; +</span>\mathrm{<span\; class="notranslate">\; R</span>}\mathrm{<span\; class="notranslate">\; 2</span>}}{\mathrm{<span\; class="notranslate">\; R</span>}\mathrm{<span\; class="notranslate">\; 2</span>}}<span\; class="notranslate">\; )</span><span\; class="notranslate">\; (</span>{\mathrm{<span\; class="notranslate">\; V</span>}}_{\mathrm{<span\; class="notranslate">\; ESR</span>}}<span\; class="notranslate">\; +</span>{\mathrm{<span\; class="notranslate">\; V</span>}}_{\mathrm{<span\; class="notranslate">\; c</span>}}<span\; class="notranslate">\; )</span><span\; class="notranslate">\; -</span><span\; class="notranslate">\; -</span><span\; class="notranslate">\; -</span><span\; class="notranslate">\; (</span>\mathrm{<span\; class="notranslate">\; 5</span>}<span\; class="notranslate">\; )</span>$

It should be noted that after passing through the voltage divider circuit ₁₀₈₄₂₆ , it can be known from equation (5 ₎ that there is approximately The multiple relationship (the cross-voltage V _ESR of the resistor R is small and negligible). Therefore, the specified voltage V _ref should also be given a similar correction. Please refer to FIG. 4 , which is a circuit diagram of an exemplary embodiment of a specific voltage gain adjustment unit 112 of the present invention. The specific voltage gain adjustment unit 112 includes an operational amplifier 1122 and a voltage divider circuit 1124, wherein the operational amplifier 1122 includes a first input terminal, a second input terminal and an output terminal, and the first input terminal is used to receive a specific voltage V _ref , the output terminal outputs a specific gain voltage V _{ref_g} . The voltage dividing circuit 1124 uses the same first resistor and the second resistor as the voltage dividing circuit 108426 to maintain the same multiplier relationship.

Finally, a control unit 110 can be used to output the upper bridge control signal S _up and the lower bridge control signal S _down according to the processed inductor output voltage V _d and the specific gain voltage V _{ref_g} . The design in the control unit 110 is mainly used to change the upper bridge control signal S _up and the lower bridge control signal S _down from logic 0 to logic 1 when the processed inductor output voltage V _d exceeds the gain specific voltage V _{ref_g} , and maintain the power supply time _Tontime length, it should be noted that, according to the different designs between the control unit 110 and the switching circuit 102, the design changes of the control method between the two are too numerous to enumerate, but as long as they are based on the same basis or can produce similar effects , all belong to the scope of the present invention. In short, the control unit 110 includes a comparator 1102 , a constant on-time unit 1104 and a non-overlap processing unit 1106 . The comparator 1102 is used to compare the processed inductor output voltage V _d and the specific gain voltage V _{ref_g} and generate a comparison result S _com . The fixed on-time unit 1104 is used for generating the power-on time control signal S _ontime according to the comparison result S _com . Then use the non-overlapping processing unit 1106 to perform non-overlapping processing before outputting the upper bridge control signal S _up and the lower bridge control signal S _down , so as to avoid the occurrence of NMOS 1022 and PMOS 1024 in the switching circuit 102. Simultaneous conduction condition.

5 is a flow chart of an embodiment of a ripple control switching regulator method according to the present invention, wherein the ripple control switching regulator method is used to control a ripple control switching regulator (switching regulator), wherein the The ripple control switching regulator includes a switch, an inductor coupled to the switch, and a capacitor coupled to the inductor. If substantially the same result can be achieved, it is not necessary to follow the order of the steps in the flow shown in FIG. 5 , and the steps shown in FIG. 5 do not have to be performed consecutively, that is, other steps can also be inserted therein. In addition, some steps in FIG. 5 can be omitted according to different embodiments or design requirements. The detailed steps are as follows:

Step S502: using the switch to selectively output a first reference voltage or a second reference voltage as an output voltage according to a control signal;

Step S504: using the inductor to generate an inductor output voltage according to the output voltage;

Step S506: Detect whether the output voltage contains double pulses and generate a detection result;

Step S508: Generate a corrected output voltage according to the detection result, the output voltage and the inductor output voltage;

Step S510: Differentiate the corrected output voltage, and generate the processed inductor output voltage

Step S512: Generate a comparison result according to the processed inductor output voltage and a predetermined voltage; and

Step S514: Generate the control signal according to the comparison result.

Those skilled in the art should be able to clearly understand steps 502 to 514 of the ripple control switching voltage stabilization method in FIG. 5 after reading the detailed descriptions of FIGS. 1 to 4 earlier in this specification. , the details will not be further explained here.

The embodiment disclosed in this specification utilizes the correction of parasitic inductance effect to avoid double pulse. At the same time, compared with the practice of directly measuring the inductor current in the traditional design, the practice of correcting the parasitic inductance effect in this specification has lower cost and less error. Minor pluses.

The above descriptions are only preferred embodiments of the present invention, and all equivalent changes and modifications made according to the patent claims of the present invention shall fall within the scope of the present invention.

Claims (13)

1. A ripple control switching regulator comprising: a switcher, used to selectively output a first reference voltage or a second reference voltage as an output voltage according to a control signal; an inductor, coupled to the switch, and generates an inductor output voltage according to the output voltage; a capacitor coupled to the inductor; an output voltage processing unit, used to output a processed inductor output voltage according to the output voltage and the inductor output voltage; and a control unit, configured to output the control signal at least according to the processed inductor output voltage; Wherein the output voltage processing unit includes: a double pulse detection unit, used to detect whether the output voltage contains double pulses and generate a detection result; and A voltage correction unit is used for generating the processed inductor output voltage according to the detection result, the output voltage and the inductor output voltage. 2. The ripple control switching regulator as claimed in claim 1, wherein the voltage correction unit comprises: a correction circuit, used to generate a correction output voltage according to the detection result, the output voltage and the inductor output voltage; and A differentiator is used to differentiate the corrected output voltage to generate the processed inductor output voltage. 3. The ripple control switching regulator as claimed in claim 2, wherein the correction circuit comprises: A first operational amplifier, including a first input terminal, a second input terminal and an output terminal, wherein the first input terminal is used to receive the inductor output voltage, and the output terminal outputs the corrected output voltage; a gain adjustment circuit having a gain value for performing a gain process on the output voltage and generating a gain output voltage at an output terminal, wherein the gain value is adjusted according to the detection result; and A first voltage divider circuit, connected in series between the output terminal of the first operational amplifier and the output terminal of the gain adjustment circuit, for generating a first divided voltage to the second input of the first operational amplifier end. 4. The ripple control switching regulator as claimed in claim 3, wherein when the detection result shows that the output voltage contains double pulses, the gain adjustment circuit adjusts the gain value. 5. The ripple control switching regulator as claimed in claim 3, further comprising a specific voltage gain adjustment unit comprising: a second operational amplifier comprising a first input terminal, a second input terminal and an output terminal, wherein the first input terminal of the second operational amplifier is used to receive a predetermined voltage; and A second voltage divider circuit, connected in series between the output terminal of the second operational amplifier and a third reference voltage, for generating a second divided voltage to the second input terminal of the second operational amplifier; Wherein the control unit outputs the control signal according to the processed inductor output voltage and the output voltage of the output terminal of the second operational amplifier. 6. The ripple control switching regulator as claimed in claim 5, wherein the first and second voltage dividing circuits have the same voltage dividing ratio. 7. The ripple control switching regulator as claimed in claim 5, wherein the first reference voltage is a supply voltage, and the second and third reference voltages are both ground voltages. 8. The ripple control switching regulator as claimed in claim 1, wherein the control unit comprises: a comparator, used to generate a comparison result according to the processed inductor output voltage and a predetermined voltage; and A control signal generation circuit is used to generate the control signal according to the comparison result. 9. A ripple control switching voltage stabilizing method for controlling a ripple control switching voltage regulator, wherein the ripple control switching voltage regulator comprises a switcher, an inductance coupled to the switcher and A capacitor is coupled to the inductor, and the ripple control switching voltage regulation method includes: using the switcher to selectively output a first reference voltage or a second reference voltage as an output voltage according to a control signal; using the inductor to generate an inductor output voltage according to the output voltage; outputting a processed inductor output voltage according to the output voltage and the inductor output voltage; and using a control unit to output the control signal at least according to the processed inductor output voltage; The step of outputting the processed inductor output voltage according to the output voltage and the inductor output voltage includes: detecting whether the output voltage contains double pulses and generating a detection result; and The processed inductor output voltage is generated according to the detection result, the output voltage and the inductor output voltage. 10. The ripple control switching voltage stabilization method according to claim 9, wherein the step of generating the processed inductor output voltage according to the detection result, the output voltage, and the inductor output voltage comprises: generating a corrected output voltage according to the detection result, the output voltage and the inductor output voltage; and The corrected output voltage is differentiated to generate the processed inductor output voltage. 11. The ripple control switching voltage stabilization method according to claim 10, wherein the step of generating the corrected output voltage according to the detection result, the output voltage and the inductor output voltage comprises: Using a first operational amplifier for negative feedback, wherein the first operational amplifier includes a first input terminal, a second input terminal and an output terminal, wherein the first input terminal is used to receive the inductor output voltage, and the output terminal outputting the corrected output voltage; performing a gain process on the output voltage to generate a gain output voltage, wherein a gain value of the gain process is adjusted according to the detection result; and Using a first voltage divider circuit to generate a first divided voltage to the second input terminal of the first operational amplifier, wherein the first voltage divider circuit is serially connected to the output terminal of the first operational amplifier and the gain output between voltages. 12. The ripple control switching voltage stabilization method according to claim 11, wherein when the detection result shows that the output voltage contains double pulses, the gain processing continuously adjusts the gain value until the detection result shows that the output voltage does not Contains double pulses so far. 13. The ripple control switching voltage stabilization method as claimed in claim 9, wherein at least the step of outputting the control signal according to the processed inductor output voltage comprises: generating a comparison result according to the processed inductor output voltage and a predetermined voltage; and The control signal is generated according to the comparison result.