CN103166474B - Primary side series connection secondary series and parallel non-contact resonant converter - Google Patents
Primary side series connection secondary series and parallel non-contact resonant converter Download PDFInfo
- Publication number
- CN103166474B CN103166474B CN201310059240.4A CN201310059240A CN103166474B CN 103166474 B CN103166474 B CN 103166474B CN 201310059240 A CN201310059240 A CN 201310059240A CN 103166474 B CN103166474 B CN 103166474B
- Authority
- CN
- China
- Prior art keywords
- primary side
- series
- contact
- parallel
- electric capacity
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
Classifications
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Landscapes
- Dc-Dc Converters (AREA)
Abstract
本发明公开一种原边串联副边串并联补偿非接触谐振变换器，属电能变换领域。它包括直流源、电压源型逆变桥、原边第一补偿电容、非接触变压器、副边第二补偿电容、副边第三补偿电容及副边整流滤波电路，并依次相连，其中电压源型逆变桥的输入端正向并联在直流源的正负两端，副边整流滤波电路的输入端并联在副边第三补偿电容的两端；通过原边第一补偿电容与非接触变压器的原边绕组串联来补偿非接触变压器的原边漏感；副边第二补偿电容与非接触变压器的副边绕组串联后再与副边第三补偿电容并联，在补偿非接触变压器副边漏感的同时还补偿非接触变压器的激磁电感。
The invention discloses a primary-side series-secondary-side series-parallel compensation non-contact resonant converter, which belongs to the field of electric energy conversion. It includes a DC source, a voltage source inverter bridge, the first compensation capacitor on the primary side, a non-contact transformer, the second compensation capacitor on the secondary side, the third compensation capacitor on the secondary side, and a rectification and filtering circuit on the secondary side, which are connected in sequence. The input terminal of the type inverter bridge is positively connected in parallel with the positive and negative ends of the DC source, and the input terminal of the secondary rectification filter circuit is connected in parallel with the two ends of the third compensation capacitor of the secondary side; through the first compensation capacitor of the primary side and the non-contact transformer The primary winding is connected in series to compensate the primary leakage inductance of the non-contact transformer; the second compensation capacitor on the secondary side is connected in series with the secondary winding of the non-contact transformer and then connected in parallel with the third compensation capacitor on the secondary side to compensate the secondary leakage inductance of the non-contact transformer. At the same time, it also compensates the excitation inductance of the non-contact transformer.
Description
技术领域technical field
本发明涉及一种适用于非接触电能传输系统的原边串联副边串并联补偿非接触谐振变换器，属于电能变换领域。The invention relates to a primary-side series-secondary-side series-parallel compensation non-contact resonant converter suitable for a non-contact electric energy transmission system, which belongs to the field of electric energy conversion.
背景技术Background technique
非接触电能传输技术利用非接触变压器实现能量的无线传递，具有使用安全方便、无机械磨损、少维护、环境适应能力强等优点，已成为业界广泛关注的新型电能传输形式。非接触变压器是非接触电能传输系统的核心元件，分离的原、副边绕组及较大的气隙使其漏感较大、激磁电感较小。因而非接触变换器必须采用多元件谐振变换器，对漏感和激磁电感分别补偿，来提高电压增益和功率传输能力，同时减小环流损耗、提高变换效率。相应的，非接触谐振变换器的补偿方式一直以来就是非接触电能传输系统研究的重点之一。在电动汽车、有轨车辆等中大功率应用场合，一般采用两级电路结构进行功率变换：前级非接触变换器实现电能的无线传输、后级的DC/DC实现输出的精确控制。相应要求补偿方式除了要使输入阻抗接近阻性保证高效率外，还应能适应负载变化和非接触变压器气隙变化保证良好的控制特性。Non-contact power transmission technology uses non-contact transformers to realize wireless transmission of energy. It has the advantages of safe and convenient use, no mechanical wear, less maintenance, and strong environmental adaptability. It has become a new form of power transmission that has been widely concerned in the industry. The non-contact transformer is the core component of the non-contact power transmission system. The separated primary and secondary windings and the large air gap make the leakage inductance large and the excitation inductance small. Therefore, the non-contact converter must use a multi-element resonant converter to compensate the leakage inductance and the magnetizing inductance separately, so as to improve the voltage gain and power transmission capacity, reduce the circulation loss and improve the conversion efficiency at the same time. Correspondingly, the compensation method of the contactless resonant converter has always been one of the focuses of the research on the contactless power transmission system. In medium and high-power applications such as electric vehicles and rail vehicles, a two-stage circuit structure is generally used for power conversion: the non-contact converter in the front stage realizes wireless transmission of electric energy, and the DC/DC in the latter stage realizes precise control of output. Corresponding requirements The compensation method should not only make the input impedance close to resistive to ensure high efficiency, but also be able to adapt to load changes and non-contact transformer air gap changes to ensure good control characteristics.
双电容补偿是目前常用的非接触谐振变换器补偿方式，包括原边串联副边串联（简称串串补偿）、原边串联副边并联（简称串并补偿）、原边并联副边串联（简称并串补偿）以及原边并联副边并联（简称并并补偿）四种补偿方式。其中串串补偿、串并补偿适用于输入电压源型逆变电路，其原边开关管电压应力较小因而应用较多。为了适应负载的变化，让谐振变换器工作在增益交点处成为众多研究人员不约而同的选择。对于串串补偿来说，其输出电压增益交点的值是固定的，与负载大小无关，也不随变压器气隙变化而改变。香港理工大学2009年发表的文章“人工心脏用非接触变换器的分析设计和控制”：Chen Q.H.,Wong S.C., and etc．Analysis, design, and control of a transcutaneous powerregulator for artificial hearts [J]．IEEE Trans on Biomedical Circuits andSystems，2009，13(1)：23-31就是分析了串/串补偿的增益交点特性，并配合非接触变压器的匝比设计使得变换器在低压满载条件下自动工作在该增益交点处获得了良好的负载动态特性。南京航空航天大学的任小永还发表了“定增益自激式非接触谐振变换器的特性和控制”一文：Ren X.Y.，Chen Q.H., and etc. Characterization and control of self-oscillating contactless resonant converter with fixed voltage gain[C]．7thInternational Power Electronics and Motion Control Conference，Harbin，2012，利用自激控制方法使得非接触谐振变换器自动工作在增益交点处。但串串补偿增益交点处输入阻抗呈感性，原边环流较大、限制了系统的效率；且增益交点处输入相角对负载的变化敏感，不适合用于两级式电路。串并补偿的增益交点处输入相角为零，适合于宽负载变化和两级式控制，在中大功率场合应用较多。但是串并补偿增益交点值并不固定，对变压器气隙变化和原副边错位敏感，在气隙较大、耦合系数较小时，增益交点数值迅速增加给后级变换带来困难。Dual capacitor compensation is a commonly used non-contact resonant converter compensation method at present, including primary side series connection and secondary side series connection (referred to as series compensation), primary side series connection and secondary side parallel connection (referred to as series parallel compensation), primary side parallel connection and secondary side series connection (referred to as Parallel compensation) and primary side parallel secondary side parallel connection (referred to as parallel compensation) four compensation methods. Among them, series-series compensation and series-parallel compensation are suitable for input voltage source inverter circuits, and the voltage stress of the primary switching tube is relatively small, so they are widely used. In order to adapt to the load change, making the resonant converter work at the gain intersection has become the unanimous choice of many researchers. For series compensation, the value of the intersection point of the output voltage gain is fixed, has nothing to do with the load size, and does not change with the change of the transformer air gap. The Hong Kong Polytechnic University published an article in 2009 "Analysis, design and control of non-contact transducers for artificial hearts": Chen Q.H., Wong S.C., and etc. Analysis, design, and control of a transcutaneous powerregulator for artificial hearts [J]. IEEE Trans on Biomedical Circuits and Systems, 2009, 13(1): 23-31 analyzed the gain intersection point characteristics of series/series compensation, and combined with the turn ratio design of the non-contact transformer, the converter automatically works at the low voltage and full load conditions. Good load dynamics are obtained at the gain intersection point. Ren Xiaoyong from Nanjing University of Aeronautics and Astronautics also published the article "Characteristics and Control of Self-oscillating Contactless Resonant Converter with Fixed Gain": Ren X.Y., Chen Q.H., and etc. Characterization and control of self-oscillating contactless resonant converter with fixed voltage gain [C]. 7thInternational Power Electronics and Motion Control Conference, Harbin, 2012, using the self-excited control method to make the non-contact resonant converter automatically work at the gain intersection point. However, the input impedance at the intersection point of the series compensation gain is inductive, and the circulating current on the primary side is large, which limits the efficiency of the system; and the input phase angle at the gain intersection point is sensitive to the change of the load, so it is not suitable for a two-stage circuit. The input phase angle at the gain intersection point of series-parallel compensation is zero, which is suitable for wide load changes and two-stage control, and is often used in medium and high power applications. However, the gain intersection value of the series-parallel compensation is not fixed, and is sensitive to the change of the transformer air gap and the misalignment of the primary and secondary sides. When the air gap is large and the coupling coefficient is small, the value of the gain intersection point increases rapidly, which brings difficulties to the subsequent stage conversion.
如何得到一种新型的补偿方式，既能具有串串补偿增益交点数值固定的优点同时还具有串并补偿增益交点与输入零相角统一的优点成为本发明设计的重点。How to obtain a new type of compensation method that can not only have the advantages of fixed series compensation gain intersection point value but also have the advantages of uniform series-parallel compensation gain intersection point and input zero phase angle has become the focus of the design of the present invention.
发明内容Contents of the invention
本发明的目的是为了克服现有补偿方式增益交点处输入阻抗相角对负载变化敏感、增益交点数值对非接触变压器气隙变化及原副边错位敏感的缺点，提出一种新型的补偿方式，提供一种适用于非接触电能传输系统中的原边串联副边串并联补偿非接触谐振变换器。它具有增益交点与输入阻抗零相角统一、增益交点数值与非接触变压器气隙变化无关的优点，可用于中大功率非接触供电系统，适于两级控制，具有良好的负载适应能力和非接触变压器气隙变化适应能力。The purpose of the present invention is to overcome the shortcomings of the existing compensation method that the input impedance phase angle at the gain intersection point is sensitive to load changes, and the value of the gain intersection point is sensitive to the change of the air gap of the non-contact transformer and the dislocation of the primary and secondary sides, and propose a new compensation method. Provided is a non-contact resonant converter with series-parallel compensation of the primary side and the secondary side, which is suitable for a non-contact power transmission system. It has the advantages of uniform gain intersection point and zero-phase angle of input impedance, gain intersection point value has nothing to do with non-contact transformer air gap changes, can be used in medium and high power non-contact power supply systems, suitable for two-stage control, has good load adaptability and non-contact Adaptability to air gap changes in contact transformers.
本发明的目的是通过以下方案实施的：The object of the present invention is implemented by the following scheme:
一种原边串联副边串并联补偿非接触谐振变换器，包括直流源(1)、电压源型逆变桥(2)、原边第一补偿电容(3)、非接触变压器(4)、副边第二补偿电容(5)、及副边整流滤波电路(7)，并依次相连，其中电压源型逆变桥的输入端正向并联在直流源的正负两端；电路中还包括副边第三补偿电容(6)；所述原边第一补偿电容(3)与非接触变压器(4)的原边绕组串联后并联在电压源型逆变桥(2)的输出端；所述非接触变压器(4)的副边绕组与副边第二补偿电容(5)串联后再与副边第三补偿电容(6)并联；副边整流滤波电路(7)的输入端也并联连接在副边第三补偿电容(6)的两端。A primary-side series-secondary-side series-parallel compensation non-contact resonant converter, comprising a DC source (1), a voltage source type inverter bridge (2), a primary-side first compensation capacitor (3), a non-contact transformer (4), The second compensation capacitor (5) on the secondary side and the rectifying and filtering circuit (7) on the secondary side are connected in sequence, wherein the input terminal of the voltage source inverter bridge is positively connected in parallel with the positive and negative ends of the DC source; the circuit also includes a secondary The third compensation capacitor (6) on the side; the first compensation capacitor (3) on the primary side is connected in series with the primary winding of the non-contact transformer (4) and connected in parallel to the output end of the voltage source inverter bridge (2); the The secondary winding of the non-contact transformer (4) is connected in parallel with the second secondary compensation capacitor (5) and then connected in parallel with the third secondary compensation capacitor (6); the input terminal of the secondary rectification filter circuit (7) is also connected in parallel Both ends of the third compensation capacitor (6) on the secondary side.
其中电压源型逆变桥(2)可以采用半桥逆变电路、全桥逆变电路、推挽式逆变电路等多种电压源型逆变电路拓扑。Among them, the voltage source inverter bridge (2) can adopt various voltage source inverter circuit topologies such as half bridge inverter circuit, full bridge inverter circuit, and push-pull inverter circuit.
其中非接触变压器(4)可以是一个非接触变压器或是多个非接触变压器串并联组合而成。The non-contact transformer (4) can be one non-contact transformer or a series-parallel combination of multiple non-contact transformers.
所述非接触变压器(4)的原边磁芯、副边磁芯采用硅钢片、铁氧体、微晶、超微晶、坡莫合金、铁钴钒等多种铁磁材料，或采用空气、陶瓷、塑料等非导磁材料。The primary side magnetic core and the secondary side magnetic core of the non-contact transformer (4) adopt various ferromagnetic materials such as silicon steel sheet, ferrite, microcrystalline, ultrafine crystal, permalloy, iron cobalt vanadium, or adopt air , ceramics, plastics and other non-magnetic materials.
所述非接触变压器(4)的原副边绕组选用实心导线、Litz线、铜皮、铜管或者PCB绕组等多种绕组形式。The primary and secondary windings of the non-contact transformer (4) are selected from a variety of winding forms such as solid wires, Litz wires, copper sheets, copper tubes or PCB windings.
其中原边第一补偿电容(3)、副边第二补偿电容(5)、副边第三补偿电容(6)可以是单一电容或是多个电容串并联组合而成。The first compensation capacitor (3) on the primary side, the second compensation capacitor (5) on the secondary side, and the third compensation capacitor (6) on the secondary side may be a single capacitor or a combination of multiple capacitors in series and parallel.
其中副边整流滤波电路(7)采用桥式整流、全波整流、倍压整流、倍流整流等多种整流滤波电路。Among them, the secondary side rectification and filtering circuit (7) adopts various rectification and filtering circuits such as bridge rectification, full-wave rectification, voltage doubler rectification, and current doubler rectification.
本发明相比现有技术有如下优点：Compared with the prior art, the present invention has the following advantages:
现有非接触谐振变换器补偿方式，或者增益交点与输入阻抗零相角点不统一，不利于提高系统效率和采用两级式控制；或者增益交点数值与非接触变压器耦合系数相关，对变压器气隙变化和原副边错位非常敏感。The existing non-contact resonant converter compensation method, or the gain intersection point and the input impedance zero-phase angle point are not uniform, which is not conducive to improving system efficiency and adopting two-stage control; or the value of the gain intersection point is related to the coupling coefficient of the non-contact transformer. It is very sensitive to gap changes and primary-secondary misalignment.
而通过本发明的原边串联副边串并联补偿非接触谐振变换器，使原边第一补偿电容(3)补偿非接触变压器原边漏感，副边第二补偿电容(5) 补偿非接触变压器副边漏感、副边第三补偿电容(6) 补偿非接触变压器的激磁电感。使得增益交点处增益数值等于非接触变压器的物理匝比，而与变压器的气隙变化无关；增益交点处输入阻抗为阻性，输入相角为零，有利于提高系统变换效率，对负载变化、气隙变化以及后级调节不敏感，可广泛用于多种非接触供电应用场合。And through the non-contact resonant converter with primary side series series and secondary side series parallel compensation compensation of the present invention, the first compensation capacitor (3) of the primary side compensates the primary side leakage inductance of the non-contact transformer, and the second compensation capacitor (5) of the secondary side compensates for the non-contact transformer. The leakage inductance of the secondary side of the transformer and the third compensation capacitor (6) of the secondary side compensate the excitation inductance of the non-contact transformer. The gain value at the gain intersection point is equal to the physical turn ratio of the non-contact transformer, and has nothing to do with the air gap change of the transformer; the input impedance at the gain intersection point is resistive, and the input phase angle is zero, which is conducive to improving the conversion efficiency of the system. The air gap change and post-stage adjustment are insensitive, and can be widely used in various non-contact power supply applications.
附图说明Description of drawings
附图1是本发明的原边串联副边串并联补偿非接触谐振变换器的电路结构示意图；Accompanying drawing 1 is the schematic diagram of the circuit structure of the primary side series secondary side series parallel compensation contactless resonant converter of the present invention;
附图2是本发明的采用对称半桥逆变电路的原边串联副边串并联补偿非接触谐振变换器的电路结构示意图；Accompanying drawing 2 is the schematic diagram of the circuit structure of the non-contact resonant converter of the present invention that adopts the primary side series series secondary side series parallel compensation of symmetrical half-bridge inverter circuit;
附图3是本发明的采用不对称半桥逆变电路的原边串联副边串并联补偿非接触谐振变换器的电路结构示意图；Accompanying drawing 3 is the schematic diagram of the circuit structure of the non-contact resonant converter of the primary side series secondary side series parallel compensation compensation non-contact resonant converter adopting the asymmetrical half-bridge inverter circuit of the present invention;
附图4是本发明的采用全桥逆变电路的原边串联副边串并联补偿非接触谐振变换器的电路结构示意图；Accompanying drawing 4 is the schematic diagram of the circuit structure of the non-contact resonant converter adopting the primary side series series secondary side series parallel compensation of the full bridge inverter circuit of the present invention;
附图5是本发明的采用推挽逆变电路的原边串联副边串并联补偿非接触谐振变换器的电路结构示意图；Accompanying drawing 5 is the schematic diagram of the circuit structure of the primary side series secondary side series parallel compensation non-contact resonant converter adopting the push-pull inverter circuit of the present invention;
附图6是本发明的采用对称半桥逆变电路和桥式整流滤波电路的原边串联副边串并联补偿非接触谐振变换器的电路结构示意图；Accompanying drawing 6 is the schematic diagram of the circuit structure of the primary side series secondary side series parallel compensation non-contact resonant converter adopting symmetrical half-bridge inverter circuit and bridge rectification filter circuit of the present invention;
附图7是本发明的采用桥式逆变电路和桥式整流滤波电路的原边串联副边串并联补偿非接触谐振变换器的电路结构示意图；Accompanying drawing 7 is the schematic diagram of the circuit structure of the primary side series secondary side series parallel compensation non-contact resonant converter adopting bridge inverter circuit and bridge rectifier filter circuit of the present invention;
附图8是本发明的原边串联副边串并联补偿非接触谐振变换器中的组合式非接触变压器的结构示意图，附图8分为图8-1、图8-2，其中附图8-1、附图8-2分别是单个非接触变压器示意图及组合式非接触变压器示意图；Accompanying drawing 8 is the structure diagram of the combined non-contact transformer in the primary side series secondary side series-parallel compensation non-contact resonant converter of the present invention, and accompanying drawing 8 is divided into Fig. 8-1, Fig. 8-2, and accompanying drawing 8 -1. Figure 8-2 is a schematic diagram of a single non-contact transformer and a schematic diagram of a combined non-contact transformer;
附图9是本发明的原边串联副边串并联补偿非接触谐振变换器的原理图，附图9分为图9-1、图9-2，其中附图9-1、附图9-2分别是串并联补偿谐振网络的基波等效电路及完全补偿时谐振网络的基波等效电路。Accompanying drawing 9 is the schematic diagram of the non-contact resonant converter with primary side series connection and secondary side series parallel compensation compensation of the present invention, and accompanying drawing 9 is divided into Fig. 9-1, Fig. 9-2, among them Fig. 9-1, Fig. 9- 2 are the fundamental wave equivalent circuit of the series-parallel compensation resonant network and the fundamental wave equivalent circuit of the fully compensated resonant network respectively.
附图10为应用例一在不同负载条件下的开环增益和输入阻抗相角的仿真曲线。附图10分为图10-1、图10-2，其中附图10-1为开环增益特性仿真结果，附图10-2为开环输入阻抗相角仿真结果。Accompanying drawing 10 is the simulation curve of open-loop gain and input impedance phase angle under different load conditions of Application Example 1. Figure 10 is divided into Figure 10-1 and Figure 10-2, wherein Figure 10-1 is the simulation result of the open-loop gain characteristic, and Figure 10-2 is the simulation result of the open-loop input impedance phase angle.
附图11为应用实例一在不同负载条件下的开环增益测试曲线。Accompanying drawing 11 is the open-loop gain test curve of application example 1 under different load conditions.
附图12为应用实例一在不同气隙条件下的闭环负载调整率测试结果。Accompanying drawing 12 is the test result of closed-loop load regulation under different air gap conditions in application example 1.
附图13为应用实例一满载时不同气隙条件下的闭环实验波形，附图13分为图13-1、图13-2，其中附图13-1为10mm气隙下的实验波形，附图13-2为15mm气隙下的实验波形。Accompanying drawing 13 is the closed-loop experimental waveform under different air gap conditions when the application example 1 is fully loaded. The accompanying drawing 13 is divided into Figure 13-1 and Figure 13-2, and the accompanying drawing 13-1 is the experimental waveform under 10mm air gap. Figure 13-2 is the experimental waveform under 15mm air gap.
附图14为应用实例二在不同气隙条件下的开环增益计算曲线。Accompanying drawing 14 is the calculation curve of open-loop gain under different air gap conditions of Application Example 2.
附图15为应用实例二采用原边恒频控制方法的负载调整率测试结果。Accompanying drawing 15 is the test result of the load adjustment rate using the primary side constant frequency control method in Application Example 2.
附图16为应用实例二满载时不同气隙条件下的实验波形。附图16分为图16-1、图16-2，其中附图16-1为12cm气隙条件下的实验波形，附图16-2为20cm气隙条件下的实验波形Accompanying drawing 16 is the experimental waveform under different air gap conditions when the second application example is fully loaded. Accompanying drawing 16 is divided into Fig. 16-1 and Fig. 16-2, wherein Fig. 16-1 is the experimental waveform under the condition of 12cm air gap, and Fig. 16-2 is the experimental waveform under the condition of 20cm air gap
附图17为应用实例二不同气隙条件下的变换器效率测试结果。Accompanying drawing 17 is the test result of converter efficiency under different air gap conditions of Application Example 2.
附图1~17中的主要符号名称：1-直流源；2-电压源型逆变桥；3-原边第一补偿电容；4-非接触变压器；5-副边第二补偿电容；6-副边第三补偿电容；7-副边整流滤波电路；C 1-原边第一补偿电容；C 2-副边第二补偿电容；C 3-副边第三补偿电容；S 1～S 4—功率管；D 1～D 4—二极管；C d1、C d2—输入分压电容；D R1~D R4—整流二极管；L f —副边整流滤波电路中的滤波电感；C f —副边整流滤波电路的滤波电容；R L —负载；V o—输出电压；A、 B—电压源型逆变桥输出端；v AB-1—逆变桥输出方波电压的基波分量；v OS —副边整流桥臂中点电压的基波分量；R E —副边整流桥、滤波环节及负载的等效电阻；n —变压器副边对原边的匝比；L l1—非接触变压器的原边漏感；L l2—非接触变压器的副边漏感；L M —非接触变压器的激磁电感；v AB —逆变桥输出方波电压；i 1—非接触变压器的原边电流；i 2—非接触变压器的副边电流；G V —输出电压增益；i C2—副边第二补偿电容两端电压。Names of main symbols in attached drawings 1 to 17: 1-DC source; 2-Voltage source type inverter bridge; 3-First compensation capacitor on the primary side; 4-Non-contact transformer; 5-Secondary compensation capacitor on the secondary side; 6 - the third compensation capacitor on the secondary side; 7 - rectification and filtering circuit on the secondary side;C 1- The first compensation capacitor on the primary side;C 2- second compensation capacitor on the secondary side;C 3- the third compensation capacitor on the secondary side;S 1~S 4- power tube;D. 1~D. 4-diode;C d1,C d2- input voltage divider capacitor;D. R1~D. R4-rectifier diode;L f —The filter inductor in the secondary side rectification filter circuit;C f —The filter capacitor of the secondary side rectification filter circuit;R L -load;V o- output voltage; A, B - voltage source inverter bridge output;v AB -1- The fundamental wave component of the square wave voltage output by the inverter bridge;v OS —The fundamental wave component of the midpoint voltage of the secondary rectifier bridge arm;R E. —Equivalent resistance of secondary side rectifier bridge, filter link and load;no - the turns ratio of the secondary side of the transformer to the primary side;L l 1— the primary side leakage inductance of the non-contact transformer;L l 2- secondary side leakage inductance of non-contact transformer;L m - the magnetizing inductance of the non-contact transformer;v AB —The inverter bridge outputs a square wave voltage;i 1- the primary current of the non-contact transformer;i 2- the secondary current of the non-contact transformer;G V — output voltage gain; i C 2- the voltage across the second compensation capacitor on the secondary side.
具体实施方式detailed description
以上附图非限制性公开了本发明的几个具体实施实例，下面结合附图对本发明作进一步描述如下。The above accompanying drawings disclose several specific implementation examples of the present invention without limitation, and the present invention will be further described below in conjunction with the accompanying drawings.
参见附图1，附图1所示为是本发明的原边串联副边串并联补偿非接触谐振变换器的电路结构示意图，直流源1及电压源型逆变桥2组成电压源型逆变电路；原边第一补偿电路3、副边第二补偿电路5、副边第三补偿电路6构成的原边串联、副边串并联补偿电路与非接触变压器4形成非接触谐振变换器的谐振网络；副边整流滤波电路7将谐振网络输出的交流信号转换为平滑的直流信号输出。Referring to accompanying drawing 1, accompanying drawing 1 shows the schematic diagram of the circuit structure of the non-contact resonant converter with primary side series connection and secondary side series connection compensation of the present invention, DC source 1 and voltage source type inverter bridge 2 form voltage source type inverter Circuit: primary side series connection, secondary side series-parallel compensation circuit composed of primary side first compensation circuit 3, secondary side second compensation circuit 5, and secondary side third compensation circuit 6 forms resonance of non-contact resonant converter with non-contact transformer 4 Network; the secondary side rectification and filtering circuit 7 converts the AC signal output by the resonant network into a smooth DC signal output.
附图2~附图5分别给出了本发明的采用对称半桥逆变电路、不对称半桥逆变电路、全桥逆变电路以及推挽逆变电路的原边串联副边串并联补偿非接触谐振变换器的电路结构示意图；其中附图5给出的推挽逆变电路的A、B输出端直接由推挽变压器的原边绕组中经抽头输出，也可采用非自耦变压器形式，则A、B端可灵活设置。逆变电路也可更换为其它电压源型逆变电路。Accompanying drawing 2～accompanying drawing 5 have respectively provided the primary side serial secondary side series-parallel compensation that adopts symmetrical half-bridge inverter circuit, asymmetrical half-bridge inverter circuit, full-bridge inverter circuit and push-pull inverter circuit of the present invention Schematic diagram of the circuit structure of the non-contact resonant converter; wherein the A and B output terminals of the push-pull inverter circuit shown in Figure 5 are directly output from the primary winding of the push-pull transformer through taps, and non-autotransformer forms can also be used , the A and B terminals can be flexibly set. The inverter circuit can also be replaced with other voltage source type inverter circuits.
附图6给出了本发明的采用对称半桥逆变电路和桥式整流滤波电路的原边串联副边串并联补偿非接触谐振变换器的电路结构示意图；附图7给出了本发明的采用桥式逆变电路和桥式整流滤波电路的原边串联副边串并联补偿非接触谐振变换器的电路结构示意图。其中电压源型逆变电路2也可更换为不对称半桥逆变电路、推挽逆变电路等其它电压源型逆变电路；整流滤波电路也可更换为倍流整流电路、全波整流电路、倍压整流滤波电路等其它形式的整流滤波电路。Accompanying drawing 6 has provided the circuit structure schematic diagram of the non-contact resonant converter that adopts symmetrical half-bridge inverter circuit and bridge rectification filter circuit of the present invention in series and secondary series-parallel compensation; Accompanying drawing 7 has provided The schematic diagram of the circuit structure of the primary-side series-secondary-side series-parallel compensation non-contact resonant converter using bridge inverter circuit and bridge rectifier filter circuit. Among them, the voltage source inverter circuit 2 can also be replaced by other voltage source inverter circuits such as an asymmetrical half-bridge inverter circuit, a push-pull inverter circuit, etc.; the rectification filter circuit can also be replaced by a current doubler rectifier circuit, a full wave rectifier circuit , Voltage doubler rectifier filter circuit and other forms of rectifier filter circuit.
附图8给出了本发明的原边串联副边串并联补偿非接触谐振变换器中的组合式非接触变压器的结构示意图。本发明中的非接触变压器既可以采用如附图8-1所示的单个非接触变压器，也可由附图8-2所示的m×n个非接触变压器组合而成。Fig. 8 shows a schematic structural diagram of the combined non-contact transformer in the non-contact resonant converter with primary-side series-secondary-side series-parallel compensation of the present invention. The non-contact transformer in the present invention can be either a single non-contact transformer as shown in Figure 8-1, or a combination of m×n non-contact transformers as shown in Figure 8-2.
下面，结合附图7给出的具体电路，采用基波分析法分析C 1、C 2、C 3及非接触变压器形成的谐振网络的等效电路，说明本发明中原边串联副边串并联补偿方式的优点：增益交点处增益数值固定，与非接触变压器的气隙变化无关；增益交点与输入零相角点统一，有利于提高系统变换效率，对负载变化及后级调节不敏感。Below, combined with the specific circuit given in Figure 7, the fundamental wave analysis method is used to analyzeC 1,C 2,C 3and the equivalent circuit of the resonant network formed by the non-contact transformer, illustrating the advantages of the primary side series-secondary side series-parallel compensation method in the present invention: the gain value at the gain intersection point is fixed, and has nothing to do with the air gap change of the non-contact transformer; the gain intersection point and the input zero The uniform phase angle point is beneficial to improve the conversion efficiency of the system, and is insensitive to load changes and post-stage adjustments.
要得到本发明中原边串联副边串并联补偿网络的等效电路首先应推导得到副边整流桥、滤波环节及负载的基波等效电路。当附图7中D R1~D R4形成的副边整流桥连续导通，其桥臂中点的电压和电流始终同相，则副边整流桥、滤波环节及负载可等效为一个线性电阻R E 。再将非接触变压器的T值等效电路模型代入，即可得到附图9-1所示的原边串联副边串并联补偿网络的基波等效模型，其中，L l1、L l2、L M分别是非接触变压器T值等效电路模型的原边漏感、副边漏感和激磁电感，v AB-1为逆变桥输出方波电压的基波分量；v OS 为副边整流桥臂中点电压的基波分量。当非接触变压器的原边漏感L l1被C 1完全补偿、副边漏感L l2被C 2完全补偿、激磁电感L M被C 3完全补偿，则附图9-1可简化为附图9-2。此时谐振网络的输出电压增益等于匝比n ，增益固定，与负载大小无关，且输入阻抗相角为零。实现了本发明预期的增益交点与输入零相角点统一、增益交点值与非接触变压器的气隙变化无关的目标。To obtain the equivalent circuit of the primary-side series-secondary-side series-parallel compensation network in the present invention, the fundamental wave equivalent circuit of the secondary-side rectifier bridge, filter link and load should be deduced first. When in attached drawing 7D. R1~D. R4The formed secondary rectifier bridge is continuously turned on, and the voltage and current at the midpoint of the bridge arm are always in phase, so the secondary rectifier bridge, filter link and load can be equivalent to a linear resistorR E. . Substituting the T-value equivalent circuit model of the non-contact transformer into it, the fundamental wave equivalent model of the primary-side series-secondary side series-parallel compensation network shown in Figure 9-1 can be obtained, where,L l1,L l2,L mare the primary side leakage inductance, secondary side leakage inductance and magnetizing inductance of the non-contact transformer T value equivalent circuit model,v AB -1Output the fundamental wave component of the square wave voltage for the inverter bridge;v OS is the fundamental wave component of the midpoint voltage of the secondary rectifier bridge arm. When the primary side leakage inductance of the non-contact transformerL l1quiltC 1Fully Compensated, Secondary Leakage InductanceL l2quiltC 2Fully compensated, magnetizing inductanceL mquiltC 3Complete compensation, then accompanying drawing 9-1 can be simplified as accompanying drawing 9-2. At this time, the output voltage gain of the resonant network is equal to the turns rationo , the gain is fixed, independent of the load size, and the input impedance phase angle is zero. The expected goal of the invention is achieved that the gain intersection point is unified with the input zero-phase angle point, and the gain intersection point value has nothing to do with the air gap change of the non-contact transformer.
应用实例一Application example one
为验证本发明的可行性，采用附图7所示的主电路和原边锁相环的控制方法，搭建了30V输入、60W输出的谐振变换器进行实验验证，具体电路参数如下所示：In order to verify the feasibility of the present invention, a resonant converter with 30V input and 60W output was built for experimental verification by using the main circuit shown in Figure 7 and the control method of the primary phase-locked loop. The specific circuit parameters are as follows:
附图10为应用实例一在不同负载条件下的开环增益和输入阻抗相角的仿真曲线，其中气隙均为10mm，等效负载R E 分别为12Ω、20Ω和60Ω。附图10-1为应用实例一的开环增益特性仿真结果。由仿真结果可以看出所提出的原边串联副边串并联补偿方式存在不同增益交点，对负载变化不敏感。对于本应用实例，仿真得到的增益交点频率为200kHz。附图10-2为应用实例一的开环输入阻抗相角仿真结果。显然，与理论分析一致，增益交点频率200kHz处的输入阻抗相角为零。Figure 10 is the simulation curve of open-loop gain and input impedance phase angle under different load conditions in Application Example 1, where the air gap is 10mm, and the equivalent load R E is 12Ω, 20Ω and 60Ω respectively. Figure 10-1 is the simulation result of the open-loop gain characteristic of Application Example 1. It can be seen from the simulation results that the proposed primary-side series-secondary-side series-parallel compensation method has different gain intersections and is not sensitive to load changes. For this application example, the simulated gain crossover frequency is 200kHz. Figure 10-2 is the simulation result of the open-loop input impedance phase angle of Application Example 1. Obviously, consistent with the theoretical analysis, the input impedance phase angle at the gain crossover frequency of 200kHz is zero.
附图11为应用实例一在不同负载条件下的开环增益测试曲线，其中气隙均为10mm，等效负载R E 分别为12Ω、20Ω和60Ω。对比附图11和附图10-1可以看出，实验测试得到的增益曲线与仿真结果基本相同：增益交点频率略有变化是由变压器及线路等效阻抗引起的；增益交点数值换算到分贝也与附图10-1基本一致。仿真分析和增益实测结果说明了理论分析的正确性，也证明了所本发明提出的原边串联副边串并联补偿方式具有增益交点和输入零相角点统一的优点。Figure 11 is the open-loop gain test curves of application example 1 under different load conditions, in which the air gap is 10mm, and the equivalent load R E is 12Ω, 20Ω and 60Ω respectively. Comparing Figure 11 with Figure 10-1, it can be seen that the gain curve obtained by the experimental test is basically the same as the simulation result: the slight change in the gain intersection frequency is caused by the transformer and the equivalent impedance of the line; the conversion of the gain intersection value to decibels is also It is basically consistent with Figure 10-1. The simulation analysis and gain measurement results illustrate the correctness of the theoretical analysis, and also prove that the primary-side series-secondary-side series-parallel compensation method proposed by the present invention has the advantage of unity of gain intersection point and input zero-phase angle point.
附图12为应用实例一在不同气隙条件下的闭环负载调整率测试结果。由附图12可见，忽略线路电阻的压降，变换器的输出与负载几乎无关，验证了本发明所提出的原边串联副边串并联补偿方式增益交点值固定，与气隙无关的基本特性。同时，附图13给出了应用实例一满载时不同气隙条件下的闭环实验波形，其中附图13-1为10mm气隙下的实验波形，13-2为15mm气隙下的实验波形。由图中可以看出原边电流i 1滞后于逆变桥桥臂中点电压v AB实现了原边开关的软开关。随着气隙和负载的变化，锁相环控制使得变换器工作在不同的开关频率。10mm气隙下满载时开关频率锁定在199kHz，而15mm时满载时开关频率则锁定在187kHz。实现了原边的锁相控制。实现开关管的软开关。Figure 12 is the test result of closed-loop load regulation under different air gap conditions in Application Example 1. It can be seen from accompanying drawing 12 that, ignoring the voltage drop of the line resistance, the output of the converter has almost nothing to do with the load, which verifies the basic characteristics of the primary-side series-secondary-side series-parallel compensation method proposed by the present invention that the gain intersection point value is fixed and has nothing to do with the air gap . At the same time, Figure 13 shows the closed-loop experimental waveforms under different air gap conditions in Application Example 1, where Figure 13-1 is the experimental waveform under 10mm air gap, and Figure 13-2 is the experimental waveform under 15mm air gap. It can be seen from the figure that the primary currenti 1Lag behind the midpoint voltage of the inverter bridge armv ABThe soft switching of the primary side switch is realized. With the change of air gap and load, the phase-locked loop control makes the converter work at different switching frequencies. The switching frequency is locked at 199kHz at full load with a 10mm air gap and at 187kHz at full load with a 15mm air gap. The phase-locked control of the primary side is realized. Realize the soft switching of the switching tube.
应用实例二Application example two
为验证本发明的可行性，采用附图7所示的主电路和原边恒频控制方法，搭建了528V输入(三相整流后的直流电压)、400V/1500W输出的谐振变换器进行实验验证，变压器气隙变化范围为10-20厘米。具体电路参数如下所示：In order to verify the feasibility of the present invention, a resonant converter with 528V input (DC voltage after three-phase rectification) and 400V/1500W output was built for experimental verification by using the main circuit shown in Figure 7 and the primary side constant frequency control method , Transformer air gap variation range is 10-20 cm. The specific circuit parameters are as follows:
附图14为应用实例二在不同气隙下的开环增益计算曲线。从图中可以看出，与理论分析相同，在不同气隙时三条曲线的增益交点值相同；且增益交点处增益曲线平坦，对频率变化不敏感，因此可选用原边恒频控制策略。根据附图14的增益曲线，选取逆变电路的开关频率为39.22k Hz时，四只开关管均为恒频开关、且占空比接近0.5，S 1、S 4同时开关、S 2、S 3同时开关，S 1 、S 3互补导通、S 2 、S 4互补导通。附图15~附图17给出的均为39.22k Hz下的测试结果。Accompanying drawing 14 is the calculation curve of open-loop gain under different air gaps of Application Example 2. It can be seen from the figure that, same as the theoretical analysis, the gain intersection values of the three curves are the same at different air gaps; and the gain curves at the gain intersection points are flat and insensitive to frequency changes, so the primary side constant frequency control strategy can be selected. According to the gain curve of accompanying drawing 14, select the switching frequency of the inverter circuit as 39.22k Hz, the four switching tubes are constant frequency switches, and the duty cycle is close to 0.5,S 1,S 4Simultaneous switch,S 2,S 3Simultaneous switch,S 1 , S 3Complementary conduction,S 2 , S 4Complementary conduction. Figures 15 to 17 are all 39.22k Test results at Hz.
实际测得应用实例二的负载调整率如附图15所示。由图可见，忽略线路电阻的压降，不同耦合系数下输出电压几乎相同，证明了本发明原边串联、副边串并联补偿方式增益交点对负载变化和气隙变换不敏感，也说明了所用恒频控制的有效性。The actual measured load regulation rate of Application Example 2 is shown in Figure 15. It can be seen from the figure that, ignoring the voltage drop of the line resistance, the output voltage is almost the same under different coupling coefficients, which proves that the gain intersection point of the compensation method of primary side series connection and secondary side series parallel connection in the present invention is not sensitive to load change and air gap transformation, and also shows that the constant effectiveness of frequency control.
附图16给出了应用实例二满载时不同气隙条件下的实验波形。由于恒频点选取在12CM情况下的增益交点处，因此12CM气隙时的循环电流比较小（如附图16-1所示），而在20CM气隙条件下电流滞后电压较多，感性较强（如附图16-2所示）。附图17为不同气隙条件下，应用实例二采用恒频控制的变换器的效率曲线。可以看出，满载时该样机10cm气隙下效率最高，达到了95.2%。实验结果证明了本发明提出的原边串联副边串并联补偿非接触谐振变换器具有增益交点固定、增益交点与输入零相角统一的特性，表明其具有易于控制、对负载变化和气隙变化不敏感，容易实现高效率等优点。Figure 16 shows the experimental waveforms under different air gap conditions when the second application example is fully loaded. Since the constant frequency point is selected at the intersection point of the gain in the case of 12CM, the circulating current at the time of the 12CM air gap is relatively small (as shown in Figure 16-1), while under the condition of the 20CM air gap, the current lags the voltage more, and the inductance is lower Strong (as shown in Figure 16-2). Accompanying drawing 17 is the efficiency curve of the converter using constant frequency control in Application Example 2 under different air gap conditions. It can be seen that the efficiency of the prototype is the highest under the 10cm air gap at full load, reaching 95.2%. The experimental results prove that the non-contact resonant converter with series-parallel compensation on the primary side and the secondary side proposed by the present invention has the characteristics of fixed gain crossing point and unity of gain crossing point and input zero phase angle, which shows that it is easy to control, stable to load changes and air gap changes Sensitive, easy to achieve high efficiency and other advantages.
Claims (7)
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201310059240.4A CN103166474B (en) | 2013-02-26 | 2013-02-26 | Primary side series connection secondary series and parallel non-contact resonant converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201310059240.4A CN103166474B (en) | 2013-02-26 | 2013-02-26 | Primary side series connection secondary series and parallel non-contact resonant converter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN103166474A CN103166474A (en) | 2013-06-19 |
| CN103166474B true CN103166474B (en) | 2017-06-30 |
Family
ID=48589270
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201310059240.4A Active CN103166474B (en) | 2013-02-26 | 2013-02-26 | Primary side series connection secondary series and parallel non-contact resonant converter |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN103166474B (en) |
Families Citing this family (13)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104515465B (en) * | 2013-09-27 | 2019-06-25 | 中兴通讯股份有限公司 | A kind of detection method and device of contactless transformer |
| GB2515597B (en) * | 2014-01-31 | 2015-05-06 | Spinnaker Int Ltd | A charging apparatus |
| CN104079081B (en) * | 2014-07-17 | 2016-06-08 | 南京矽力杰半导体技术有限公司 | Mode of resonance contactless power supply device and integrated circuit |
| CN104242657B (en) * | 2014-08-29 | 2017-05-03 | 南京航空航天大学 | Non-contact resonant converter with primary side parallel and series connection compensation and secondary side series connection compensation |
| US9815381B2 (en) * | 2015-02-27 | 2017-11-14 | Qualcomm Incorporated | Systems, methods, and apparatus for partial electronics integration in vehicle pads for wireless power transfer applications |
| CN105048812B (en) * | 2015-07-17 | 2018-09-28 | 许继电源有限公司 | A kind of LLC resonance circuits |
| CN105226952B (en) * | 2015-09-18 | 2018-10-12 | 中国矿业大学 | A kind of constant current constant frequency inductively Transmission system and its design method |
| CN105699737A (en) * | 2016-03-04 | 2016-06-22 | 胜利油田胜利电器有限责任公司 | Resonant injection signal extraction sensor |
| CN106300986B (en) * | 2016-08-03 | 2019-07-05 | 深圳市盛弘电气股份有限公司 | Switching Power Supply |
| CN106411165B (en) * | 2016-11-09 | 2019-12-20 | 深圳市拓革科技有限公司 | Resonant inverter circuit and control method thereof |
| CN112350579B (en) * | 2020-10-22 | 2022-03-18 | 南京邮电大学 | A Design Method of Secondary Side Parameters Adapting to Arbitrary Primary Side Series Compensation WPT System |
| CN114094954A (en) * | 2021-11-09 | 2022-02-25 | 复旦大学 | A High Flatness Interstage Matching Circuit |
| CN120090492B (en) * | 2025-04-30 | 2025-07-01 | 杭州日芝电气有限公司 | Full-bridge inversion series resonance intermediate frequency induction power supply with autotransformer and control method |
Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1996711A (en) * | 2006-12-08 | 2007-07-11 | 广州电器科学研究院 | Inductive coupled wireless power transfer device |
| CN101540545A (en) * | 2009-04-28 | 2009-09-23 | 大连理工大学 | Non-contact electric energy transmission system based on single-phase matrix convertor |
| CN101697453A (en) * | 2009-10-22 | 2010-04-21 | 北京金自天正智能控制股份有限公司 | System for generating high-stability high voltage |
| CN102005930A (en) * | 2009-09-03 | 2011-04-06 | 天津工程师范学院 | Non-contact electric energy transmission system |
| CN102064707A (en) * | 2011-01-21 | 2011-05-18 | 浙江大学 | Input parallel and output parallel combination converter under control of common phase-shifting angle |
| CN102522900A (en) * | 2011-11-18 | 2012-06-27 | 南京航空航天大学 | Fixed-gain self-excited non-contact resonant converter and control method thereof |
Family Cites Families (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102857134B (en) * | 2012-10-09 | 2014-11-26 | 中国科学院电工研究所 | High-frequency inverter power supply of wireless power transmission device and frequency doubling control method for inverter power supply |
-
2013
- 2013-02-26 CN CN201310059240.4A patent/CN103166474B/en active Active
Patent Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1996711A (en) * | 2006-12-08 | 2007-07-11 | 广州电器科学研究院 | Inductive coupled wireless power transfer device |
| CN101540545A (en) * | 2009-04-28 | 2009-09-23 | 大连理工大学 | Non-contact electric energy transmission system based on single-phase matrix convertor |
| CN102005930A (en) * | 2009-09-03 | 2011-04-06 | 天津工程师范学院 | Non-contact electric energy transmission system |
| CN101697453A (en) * | 2009-10-22 | 2010-04-21 | 北京金自天正智能控制股份有限公司 | System for generating high-stability high voltage |
| CN102064707A (en) * | 2011-01-21 | 2011-05-18 | 浙江大学 | Input parallel and output parallel combination converter under control of common phase-shifting angle |
| CN102522900A (en) * | 2011-11-18 | 2012-06-27 | 南京航空航天大学 | Fixed-gain self-excited non-contact resonant converter and control method thereof |
Non-Patent Citations (1)
| Title |
|---|
| 非接触电能传输系统频率分叉现象研究;韩腾等;《电工电能新技术》;20050423;第24卷(第02期);44-47,76 * |
Also Published As
| Publication number | Publication date |
|---|---|
| CN103166474A (en) | 2013-06-19 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN103166474B (en) | Primary side series connection secondary series and parallel non-contact resonant converter | |
| CN104753152B (en) | The induction type charging system of constant current constant voltage Compound Topology | |
| CN109130903B (en) | A low-voltage high-power wireless charging system with double-sided LCCL-T topology | |
| CN104242657B (en) | Non-contact resonant converter with primary side parallel and series connection compensation and secondary side series connection compensation | |
| US10217559B2 (en) | Multiphase coupled and integrated inductors with printed circuit board (PBC) windings for power factor correction (PFC) converters | |
| CN111342668B (en) | A method to expand the soft switching range of SS structure WPT system by using variable inductance | |
| CN104617685B (en) | A kind of contact inductive electric energy transmission control unit and method thereof | |
| CN110829619B (en) | A transmission line energy taking device with impedance adjustment function and its application method | |
| Song et al. | A control strategy for wireless EV charging system to improve weak coupling output based on variable inductor and capacitor | |
| CN103248234B (en) | Control method applied to bidirectional isolation full-bridge current transformer for battery energy storage | |
| CN111532151B (en) | Wireless charging system and method for electric automobile | |
| Wu et al. | Design of symmetric voltage cancellation control for LCL converters in inductive power transfer systems | |
| Wei et al. | A self-oscillation WPT system with high misalignment tolerance | |
| CN103762846A (en) | Magnetic integrated resonant converter | |
| CN107579659B (en) | Constant current resonant DC conversion circuit and method adapting to high parasitic parameters of transformer | |
| CN105846683A (en) | Efficient wide-range voltage regulation SP/S resonance compensation electric automobile wireless charging topological structure | |
| Wang et al. | Constant-current and constant-voltage output using hybrid compensated single-stage resonant converter for wireless power transfer | |
| CN111312490A (en) | PCB active planar transformer and manufacturing method thereof | |
| Mai et al. | Analysis, design, and optimization of the IPT system with LC filter rectifier featuring high efficiency | |
| WO2025130148A1 (en) | Transformer structure for llc resonant converter | |
| Guo et al. | Multiparallel and flexible expansion of single-switch WPT inverter by magnetic integration | |
| CN107733093A (en) | A kind of Capacitance Coupled resonance type wireless energy transmission system and method | |
| CN105720693B (en) | The Parameters design of load soft handover is realized in a kind of ECPT systems | |
| CN105991044B (en) | Non-contact power supply secondary side rectifying circuit and method | |
| CN115276256B (en) | Bidirectional MC-WPT system and constant-current output phase-shifting control method thereof |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |