CN103532372B - Multi-phase DC to DC power conversion device - Google Patents

Abstract

Disclosed herein is a multi-phase DC-DC power conversion device, which comprises at least one DC-DC power conversion module. Each DC-DC power conversion module at least comprises a first output inductor, a second output inductor and a current detector. The current detector is used for sensing the current passing through the first output inductor and the second output inductor and comprises a first resistor, a first capacitor, a second resistor, a second capacitor and a third resistor. The third resistor is directly or indirectly coupled between the first capacitor and the load circuit, and the third resistor is directly or indirectly coupled between the second capacitor and the load circuit, so that when the first capacitor is in a charging state, part of a charging current for charging the first capacitor flows through the second capacitor.

Description

Multi-phase DC to DC power conversion device

technical field

The invention relates to a DC-to-DC power conversion device, in particular to a multi-phase DC-to-DC power conversion device.

Background technique

With the development of science and technology, various electronic devices are widely used in people's life. Different electronic devices, or different circuits under the same electronic device, often require different DC supply voltages. Therefore, a stable and reliable DC-to-DC power conversion device becomes more and more important.

Generally speaking, the upper limit of a single-phase power conversion device is about 30 amperes, and its conversion efficiency will drop rapidly after exceeding 30 amperes. Therefore, if you want to use a device that needs high current drive, such as a computer or a car, you must choose to use a multi-phase power conversion device. However, the multi-phase power conversion device has the problem of uneven current in each phase. When the current is excessively biased in a certain phase, it may lead to poor conversion efficiency, unstable circuit, or overheating of parts and damage.

Therefore, a multi-phase power conversion device with average output current of each phase should be proposed.

Contents of the invention

One aspect of the present invention is to provide a multi-phase DC-to-DC power conversion device, in which the current of each phase can be output on average.

According to an embodiment of the present invention, a multi-phase DC-to-DC power conversion device includes a pulse width modulation module, a current feedback processing module, and at least one DC-to-DC power conversion module. The pulse width modulation module is used to generate multiple sets of control pulses. The DC-DC power conversion module includes a first output inductor, a second output inductor, a first switch, a second switch and a current detector. The first switch is coupled to the first output inductor, and the first switch receives the control pulse to control the current of the first output inductor. The second switch is coupled to the second output inductor, and the second switch receives another control pulse to control the current of the second output inductor. The current detector is connected in parallel with the first and second output inductors to sense the current passing through the first output inductor and the second output inductor, wherein the current feedback processing module adjusts in real time according to the sensed current Control the duty cycle of the pulse. The current detector includes a first resistor, a first capacitor, a second resistor, a second capacitor and a third resistor. The first resistor is connected in series with the first capacitor. The second resistor is connected in series with the second capacitor. The third resistor is directly or indirectly coupled between the first capacitor and the load circuit, and the third resistor is directly or indirectly coupled between the second capacitor and the load circuit, so that when the first capacitor is in a charging state, the first capacitor is charged. Part of the charging current for charging the capacitor flows through the second capacitor, so that when the second capacitor is in a charging state, part of the charging current for charging the second capacitor flows through the first capacitor.

According to an embodiment of the present invention, the first end of the first resistor, the first end of the first output inductor, and the first switch are coupled to each other, and the second end of the first resistor is coupled to the first end of the first capacitor. end, the second end of the first capacitor is coupled to the first end of the third resistor, and the second end of the third resistor, the second end of the first output inductor, the second end of the second output inductor and the load circuit coupled to each other.

According to an embodiment of the present invention, the first end of the second resistor, the first end of the second output inductor, and the second switch are coupled to each other, and the second end of the second resistor is coupled to the first end of the second capacitor. end, the second end of the second capacitor is coupled to the first end of the third resistor, and the second end of the third resistor, the second end of the first output inductor, the second end of the second output inductor and the load circuit coupled to each other.

According to an embodiment of the present invention, the control pulse used to control the first switch and the control pulse used to control the second switch are in opposite phases.

According to an embodiment of the present invention, when the first capacitor is in a charging state, the second capacitor is in a discharging state. When the second capacitor is in the charging state, the first capacitor is in the discharging state.

According to an embodiment of the present invention, the resistance of the third resistor is less than or equal to the resistance of the first resistor, and the resistance of the third resistor is less than or equal to the resistance of the second resistor.

According to an embodiment of the present invention, the first switch includes a first high-side switch, and the second switch includes a second high-side switch.

According to an embodiment of the present invention, the first switch further includes a first low-side switch coupled to the first high-side switch. The second switch further includes a second low-side switch coupled to the second high-side switch.

According to an embodiment of the present invention, the resistance value of the third resistor can be adjusted when the current value of the first and second output inductors sensed by the current detector is zero and the actual value of the first and second output inductors The time difference when the inductor current is zero.

According to an embodiment of the present invention, a voltage feedback processing module and a voltage dividing module of a multi-phase DC-DC power conversion device. The voltage divider module is used to disperse the output voltage applied to the load circuit by the DC-to-DC power conversion module, including a first voltage divider resistor and a second voltage divider resistor, wherein the first voltage divider resistor and the second voltage divider resistor are connected in series, and the voltage The feedback processing module makes the pulse width modulation module adjust the duty cycle of the control pulse according to the voltage across the second voltage dividing resistor.

Through the above-mentioned embodiments, a multi-phase DC-to-DC power conversion device can be realized. Wherein, through the voltage across each capacitor in the current detector, the current passing through the first and second output inductors can be reflected in real time, so that the pulse width modulation module can adjust the duty cycle of the control pulse wave in real time, and avoid The current flowing through each output inductor is uneven. By adjusting the third resistor in the current detector, the time difference between the actual current flowing through each output inductor falling to zero and the current sensed by the current detector falling to zero can be further adjusted, and the multi-phase DC Finer adjustment and control of DC power conversion devices.

Description of drawings

In order to make the above and other objects, features, advantages and embodiments of the present invention more comprehensible, the accompanying drawings are described as follows:

FIG. 1 is a circuit diagram of a multi-phase DC-DC power conversion device according to an embodiment of the present invention;

2 is a circuit diagram of a multi-phase DC-DC power conversion device according to an embodiment of the present invention;

FIG. 3 is an equivalent circuit diagram drawn according to the current detector in FIG. 1;

FIG. 4 shows the current flowing through the first and second output inductors, the voltage across the first and second capacitors, and the current flowing through the first and second output inductors according to the multi-phase DC-to-DC power conversion device shown in FIG. 1. A simulation diagram of the current of the capacitor and the current flowing through the third resistor;

FIG. 5 is a diagram illustrating the multi-phase DC-to-DC power conversion device in FIG. 1. When the current flowing through the first output inductor is discontinuous and the third resistance is 2kΩ, the current flowing through the first output inductor is the same as that of the first output inductor. Simulation diagram of the voltage across the capacitor;

FIG. 6 is a diagram illustrating the multi-phase DC-to-DC power conversion device shown in FIG. 1. When the current flowing through the first output inductor is discontinuous and the third resistor is 0k, the current flowing through the first output inductor is the same as that of the first output inductor. A simulated plot of the voltage across a capacitor.

[Description of main component symbols]

10: Load circuit 100: Multi-phase DC to DC power conversion device

110: clock generation module 120: pulse width modulation module

130: Current feedback processing module 140: DC to DC power conversion module

142: first switcher 144: second switcher

146: Current detector 150: Voltage feedback processing module

R1: first resistor R2: second resistor

R3: the third resistor C1: the first capacitor

C2: second capacitor L1: first output inductor

L2: Second output inductor Q1: First high-side switcher

Q2: First low-side switcher Q3: Second high-side switcher

Q4: second low-side switcher D1-D4: diode

R _F1 : the first voltage divider resistor R _F2 : the second voltage divider resistor

C _O : output capacitance V _O : output voltage

DCR1: Resistor DCR2: Resistor

V _L1 : Voltage V _L2 : Voltage

V _C1 : Voltage V _C1 : Voltage

I _L1 : current I _L2 : current

I _C1 : Current I _C1 : Current

I _R3 : current t _{0 , IL1} : time point

t _0,VC1 : time point I _C1,R3 : current

I _C2,R3 : Current I _C1,C2 : Current

I _C2,C1 : Current

detailed description

The following will clearly illustrate the spirit of the present invention with the accompanying drawings and detailed descriptions. After any person with ordinary knowledge in the technical field understands the preferred embodiments of the present invention, he can change and modify it by the technology taught by the present invention. without departing from the spirit and scope of the present invention.

One aspect of the present invention is to provide a multi-phase DC-to-DC power conversion device, in which the current of each phase can be output on average.

FIG. 1 is a circuit diagram of a multi-phase DC-DC power conversion device 100 according to an embodiment of the present invention. The multi-phase DC-DC power conversion device 100 includes a clock generation module 110 , a pulse width modulation module 120 , a current feedback processing module 130 and at least one DC-DC power conversion module 140 . In this embodiment, each of the above-mentioned modules can be realized by hardware circuits. In addition, the multi-phase DC-to-DC power conversion device 100 of this embodiment only includes one DC-to-DC power conversion module 140, and the number of phases is 2 phases. However, in other embodiments, the multi-phase DC-to-DC power conversion device The 100 may include two, three or more DC-DC power conversion modules 140, so the number of phases may be 4, 6 or more.

The clock generating module 110 is used for generating a driving clock to drive the PWM module 120 . The pulse width modulation module 120 is used for generating multiple sets of control pulses according to the driving clock. The output voltage V _O of the multi-phase DC-DC power conversion device 100 can be determined by controlling the duty cycle of the pulse wave. The current feedback processing module 130 is used to receive the feedback signal from the DC-to-DC power conversion module 140, so that the pulse width modulation module 120 can adjust the control pulse when the output current of the DC-to-DC power conversion module 140 is too large or too small. working cycle.

The DC-DC power conversion module 140 may include a first output inductor L1 , a second output inductor L2 , a first switch 142 , a second switch 144 , a diode D1 , a diode D2 and a current detector 146 .

Structurally, the first switch 142 is coupled to the input power V _IN , the PWM module 120 and the first output inductor L1, and the second switch 144 is coupled to the input power V _IN and the PWM module. 120 and the second output inductor L2 , the first output inductor L1 is coupled to the diode D1 and the load circuit 10 , and the second output inductor L2 is coupled to the diode D1 and the load circuit 10 . The current detector 146 is connected in parallel to the first and second output inductors L1 and L2 and coupled to the current feedback processing module 130 .

In operation, the pulse width modulation module 120 provides anti-phase control pulses to the first switch 142 and the second switch 144 respectively. When the first switch 142 is in the first operating state, the input power V _IN is coupled to the first output inductor L1, and the current flows from the input power V _IN through the first switch 142, the first output inductor L1 to the load circuit 10 and store charges in the output capacitor C _O of the load circuit 10 . At this time, the first output inductor L1 stores energy due to the current passing through. When the first switch 142 is in the second operating state, the input power V _IN and the first output inductor L1 are disconnected, and one end of the first output inductor L1 starts to release the stored energy to the load circuit 10, and returns to the load circuit 10 through the diode D1. the other end of the first output inductor L1. Similarly, the operation of the second switch 144 is also the same, but its operation is opposite to that of the first switch 142 . Therefore, the currents I _L1 and I _L2 flowing through the first and second output inductors L1 and L2 can charge the output capacitor C _O of the load circuit 10 in turn, and provide a stable output voltage V _O through the output capacitor C _O to Achieve DC to DC power conversion. In addition, the current detector 146 senses the currents I _L1 and I _L2 passing through the first and second output inductors L1 and L2 respectively, and the current feedback processing module 130 senses the current I _L1 according to the current detector 146 , I _L2 , to adjust the duty cycles of the control pulses sent to the first and second switches 142 and 144 in real time, so as to avoid circuit components being damaged due to overload. It should be noted that, in this embodiment, the control pulses provided to the first and second switches 142 and 144 are opposite to each other, in order to make the current I _L1 flowing through the first and second output inductors L1 and L2 , I _L2 evenly charges the output capacitor C _O in time. However, those skilled in the art can design the phase difference of the control pulses provided to the first and second switches 142 and 144 according to different applications, and are not limited to the phase difference in this embodiment.

In this embodiment, the first switch 142 may include a first high-side switch Q1 and a first low-side switch Q2 connected in series, and the second switch 144 may include a second high-side switch Q3 connected in series. and the second low-side switch Q4, and the on or off of the switches Q1, Q2, Q3 and Q4 are all controlled by the control pulse. The first low-side switch Q2 is connected in parallel with the diode D1, and the second low-side switch Q4 is connected in parallel with the diode D2. The first and second low-side switches Q2 and Q4 can be turned on when the first and second switches 142 and 144 are in the second operating state, replacing the diodes D1 and D2 with a lower forward bias voltage as the current path . Those skilled in the art should clearly understand that the first and second low-side switches Q2 and Q4 may include a body diode, so the diodes D1 and D2 may be omitted in some embodiments. However, the energy loss of the internally connected diodes under forward bias is generally greater than that of ordinary diodes, so in this embodiment, the diodes D1 and D2 are still connected in parallel on the first and second low-side switches Q2 and Q4.

The current detector 146 can be a circuit structure, which can include a first resistor R1, a first capacitor C1, a second resistor R2, a second capacitor C2 and a third resistor R3. The first end of the first resistor R1, the first end of the first output inductor L1, and the node connecting the first high-side switch Q1 to the first low-side switch Q2 are coupled to each other, and the second end of the first resistor R1 is coupled to each other. connected to the first terminal of the first capacitor C1, the second terminal of the first capacitor C1 is coupled to the first terminal of the third resistor R3, the first terminal of the second resistor R2, the first terminal of the second output inductor L2 and the first terminal of the second output inductor L2 Nodes of the two high-side switch Q3 connected to the second low-side switch Q4 are coupled to each other, the second terminal of the second resistor R2 is coupled to the first terminal of the second capacitor C2, and the second terminal of the second capacitor C2 is coupled to the first terminal of the second capacitor C2. The first end of the three resistors R3 , the second end of the third resistor R3 , the second end of the first output inductor L1 , the second end of the second output inductor L2 and the load circuit 10 are coupled to each other. Those skilled in the art will clearly understand that the positions of the first capacitor C1 and the first resistor R1 connected in series can be reversed without substantially changing the circuit, and that the positions of the second capacitor C2 and the second resistor R2 connected in series The positions can also be reversed. Therefore, the third resistor R3 may be directly or indirectly coupled between the first capacitor C1 and the load circuit 10 , and the third resistor R3 may also be directly or indirectly coupled between the second capacitor C2 and the load circuit 10 .

FIG. 2 is a circuit diagram of a multi-phase DC-DC power conversion device 100 according to an embodiment of the present invention. This embodiment is substantially similar to the embodiment shown in FIG. 1 , so details are not repeated here. The difference between the two is that, in this embodiment, the first and second low-side switches Q2 and Q4 can be replaced by diodes D3 and D4. In this way, the PWM module 120 does not need to additionally provide control pulses to turn on the first and second low-side switches Q2 and Q4, thus reducing the complexity of the design of the PWM module 120 .

In addition, in some other embodiments, the multi-phase DC-DC power conversion device 100 may further include a voltage feedback processing module 150 and voltage dividing modules R _F1 , R _F2 . The voltage-dividing modules R _F1 and R _F2 are used to disperse the output voltage V _O supplied to the load circuit 10 by the DC-DC power conversion module 140, including a first voltage-dividing resistor R _F1 and a second voltage-dividing resistor R _F2 . The piezoelectric resistor R _F1 and the second voltage dividing resistor R _F2 are connected in series, and the voltage feedback processing module 150 makes the pulse width modulation module 120 adjust the duty cycle of the control pulse according to the voltage across the second voltage dividing resistor R _F2 . Through the settings of the voltage feedback processing module 150 and the voltage divider modules R _F1 and R _F2 , the pulse width modulation module 120 can pass the output current and the output voltage at the same time to adjust the duty cycle of the control pulse and avoid the Electronic components are destroyed due to overload.

In order to make the present invention easier to understand, the operation of the current detector 146 is further described below through FIG. 3 . FIG. 3 is an equivalent circuit diagram based on the current detector 146 shown in FIG. 1 . Among them, V _L1 and V _L2 are the voltage across the first and second output inductors L1 and L2, and the first and second output inductors L1 and L2 include the first and second Wound resistances DCR1 and DCR2 of the two output inductors L1 and L2. Therefore, by design, the product of the resistance value of the first resistor R1, the capacitance value of the first capacitor C1 and the resistance value of the resistor DCR1 is the inductance value of the first output inductor L1, then the voltage V _{C1 across both ends of the first capacitor C1} may be roughly proportional to the current I _{L1 flowing through the first output inductor L1} . And the product of the resistance value of the second resistor R2, the capacitance value of the second capacitor C2 and the resistance value of the resistor DCR2 is the inductance value of the second output inductor L2, then the voltage across the second capacitor C2 V _C2 can be roughly proportional to The current I _{L2 flowing through the second output inductor L2} . Therefore, according to the voltages V _C1 and V _C2 across the first and second capacitors C1 and C2 , the current detector 146 can measure the currents I _L1 and I _{L2 flowing through the first and second output inductors L1 and L2} .

In addition, the third resistor R3 is blocked between the first capacitor C1 and the load circuit 10, and between the second capacitor C2 and the load circuit 10, so that when V _L1 is at a high potential and V _L2 is at a low potential, the first When a capacitor C1 is in a charging state and the second capacitor C2 is in a discharging state, part of the current I _C1 that charges the first capacitor C1 flows to the second capacitor C2 and the second resistor R2, such as the current I _{C1, C2} (the rest of I _C1 The current flows to the third resistor R3, such as the current I _C1,R3 ). When V _L1 is a low potential and V _L2 is a high potential, so that the second capacitor C2 is in a charging state and the first capacitor C1 is in a discharging state, part of the current I _C2 charging the second capacitor C2 flows to the first capacitor C1 and the first resistor R1, such as the current I _C2,C1 (the remaining current of I _C2 flows to the third resistor R3, such as the current I _C2,R3 ).

In addition, if the currents I _L1 and I _L2 flowing through the first and second output inductors L1 and L2 are discontinuous, the first capacitor C1 and the second capacitor C2 are charged and discharged to each other, so that the first The time for the voltage V _C1 across the two ends of the capacitor C1 to drop to zero lags behind the time for the current I _L1 flowing through the first output inductor L1 to drop to zero, and the time for the voltage V _C2 across the two ends of the second capacitor C2 to drop to zero The time lags behind the time when the current I _L2 flowing through the second output inductor L2 drops to zero. When the resistance value of the third resistor R3 is larger, the time for the voltages V _C1 and V _C2 to drop to zero is longer than the time for the currents I _L1 and I _L2 to drop to zero. The resistance value of the third resistor R3 can adjust the currents of the first and second output inductors I _L1 and I _L2 sensed by the current detector 146 to be zero (that is, the voltages V _C1 and V _C2 are zero) The time difference from when the currents I _L1 and I _L2 actually flowing through the first and second output inductors L1 and L2 are zero.

FIG. 4 shows currents I _L1 , I _L2 , first and second capacitors C1 and C2 flowing through the first and second output inductors L1 and L2 according to the multi-phase DC-DC power conversion device 100 shown in FIG. 1 A simulation diagram of the transvoltages V _C1 and V _C2 at both ends, the currents I _C1 and I _C2 flowing through the first and second capacitors C1 and C2 , and the current I _R3 flowing through the third resistor R3 . As shown in FIG. 4 , the voltages V _C1 and V _C2 across the first and second capacitors C1 and C2 are roughly proportional to the currents I _L1 and I _{L2 flowing through the first and second output inductors L1 and L2} . During the period T1, the input power supply V _IN is coupled to the first output inductor L1, the first capacitor C1 is in a charging state, and the current I C1 flowing through the first capacitor _C1 and the current I _R3 flowing through the third resistor R3 are positive. current, and the current I _C2 flowing through the second capacitor C2 is a negative current. During the period T2, the input power supply V _IN and the first output inductor L1 are disconnected, the first capacitor C1 is in a discharging state, the current I C1 flowing through the first capacitor _C1 and the current I _R3 flowing through the third resistor R3 are negative currents . Similarly, during the period T3, the input power supply V _IN is coupled to the second output inductor L2, the second capacitor C2 is in the charging state, the current I _C2 flowing through the second capacitor C2 and the current I flowing through the third resistor R3 _R3 is a positive current, and the current IC1 flowing through the first capacitor C1 is a negative current. During the period T4, the input power supply V _IN and the second output inductor L2 are disconnected, the second capacitor C2 is in a discharging state, the current I C2 flowing through the second capacitor _C2 and the current I _R3 flowing through the third resistor R3 are negative currents .

FIG. 5 shows the multi-phase DC-to-DC power conversion device 100 shown in FIG. 1. When the current flowing through the first output inductor L1 is discontinuous and the third resistor R3 is 2kΩ, the current flowing through the first output inductor L1 A simulation diagram of the current I _L1 and the voltage V _C1 across the first capacitor C1 . As shown in FIG. 5 , the time point when the current I _L1 flowing through the first output inductor L1 reaches zero is t _0,IL1 , and the time point when the voltage across the first capacitor C1 V _C1 reaches zero is t _{0 , VC1} . The time difference between the time points t _{0 , IL1} and t _0VC1 can be used to fine-tune the multi-phase DC-DC power conversion device 100 , for example, the timing of turning off the first and second low-side switches Q2 and Q4 by the control pulse can be adjusted. When the third resistor R3 is larger, the time difference between the time point t _0,IL1 and t _0,VC1 is larger, and vice versa. In order to prevent the difference between the voltage V _C1 across the first capacitor C1 and the current I _L1 flowing through the first output inductor L1 from being too large, the resistance of the third resistor R3 is less than or equal to the resistance of the first resistor R1, And the resistance value of the third resistor R3 is less than or equal to the resistance value of the second resistor R2. When the third resistor R3 is 0Ω, the time point t _0,IL1 is the same as t _0,VC1 , and the voltage V _C1 is proportional to the current I _L1 , as shown in FIG. 6 .

Although the present invention has been disclosed above with the embodiments, it is not intended to limit the present invention. Any skilled person can make various changes and modifications without departing from the spirit and scope of the present invention. Therefore, the present invention The scope of protection should be based on the scope defined by the appended claims.

Claims (9)

1. a multi-phase DC-DC power converter, is characterized in that, comprising:

One pulse wave width modulation module, controls pulse wave in order to produce many groups;

One electric current back coupling processing module; And

At least one direct current, to DC power supply modular converter, comprising:

One first output inductor;

One second output inductor;

One first derailing switch, couples this first output inductor, and this first derailing switch receives this control pulse wave to control the electric current of this first output inductor;

One second switch device, couples this second output inductor, and this second switch device receives another this control pulse wave to control the electric current of this second output inductor; And

One current detector, be parallel to this first, second output inductor, in order to sense the electric current by this first output inductor and this second output inductor, wherein this electric current feedbacks processing module according to sensed electric current, immediately to adjust the work period that those control pulse wave, and wherein this current detector comprises: one first resistance, one first electric capacity, one second resistance, one second electric capacity and one the 3rd resistance, this first electric capacity of this first resistant series, this second electric capacity of this second resistant series, 3rd resistance is directly or indirectly coupled between this first electric capacity and a load circuit, and the 3rd resistance is directly or indirectly coupled between this second electric capacity and this load circuit, make when this first electric capacity is in charged state, this the second electric capacity is flowed through to a charging current part of this first capacitor charging, and make when this second electric capacity is in charged state, this the first electric capacity is flowed through to another charging current part of this second capacitor charging,

Wherein the resistance value of the 3rd resistance is less than or equal to the resistance value of this first resistance, and the resistance value of the 3rd resistance is less than or equal to the resistance value of this second resistance.

2. multi-phase DC-DC power converter according to claim 1, it is characterized in that, the first end of this first resistance, the first end of this first output inductor and this first derailing switch are coupled to each other, second end of this first resistance couples the first end of this first electric capacity, second end of this first electric capacity couples the first end of the 3rd resistance, and the second end of the 3rd resistance, the second end of this first output inductor, the second end of this second output inductor and this load circuit are coupled to each other.

3. multi-phase DC-DC power converter according to claim 1, it is characterized in that, the first end of this second resistance, the first end of this second output inductor and this second switch device are coupled to each other, second end of this second resistance couples the first end of this second electric capacity, second end of this second electric capacity couples the first end of the 3rd resistance, and the second end of the 3rd resistance, the second end of this first output inductor, the second end of this second output inductor and this load circuit are coupled to each other.

4. multi-phase DC-DC power converter according to claim 1, is characterized in that, anti-phase with the control pulse wave in order to control this second switch device in order to the control pulse wave controlling this first derailing switch.

5. multi-phase DC-DC power converter according to claim 1, is characterized in that, when this first electric capacity is in charged state, this second electric capacity is discharge condition; And when this second electric capacity is in charged state, this first electric capacity is discharge condition.

6. multi-phase DC-DC power converter according to claim 1, is characterized in that, this first derailing switch comprises one first high-side switch device, and this second switch device comprises one second high-side switch device.

7. multi-phase DC-DC power converter according to claim 6, it is characterized in that, this first derailing switch also comprises one first low side switch device, couples this first high-side switch device, and wherein this second switch device also comprises one second low side switch device, couple this second high-side switch device.

8. multi-phase DC-DC power converter according to claim 1, it is characterized in that, the time difference that the resistance value of the 3rd resistance is this current detector of adjustable when being zero point with the electric current actually by this first, second output inductor when to sense by the current value of this first, second output inductor be zero point.

9. multi-phase DC-DC power converter according to claim 1, also comprises:

One voltage feedback processing module; And

One division module, in order to disperse this direct current, one output voltage of this load circuit is bestowed to DC power supply modular converter, comprise one first divider resistance and one second divider resistance, wherein this first divider resistance and this second divider resistance are one another in series, and this voltage feedback processing module controls work period of pulse waves according to the cross-pressure on this second divider resistance to make this pulse wave width modulation module adjust those.