CN115133917A - Power tube driving circuit and power tube driving method - Google Patents
Power tube driving circuit and power tube driving method Download PDFInfo
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- CN115133917A CN115133917A CN202110335392.7A CN202110335392A CN115133917A CN 115133917 A CN115133917 A CN 115133917A CN 202110335392 A CN202110335392 A CN 202110335392A CN 115133917 A CN115133917 A CN 115133917A
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Abstract
The disclosure relates to a power tube driving circuit and a power tube driving method. The power tube driving circuit comprises an input module, an output module and a transformer, wherein the input module is connected with the output module through the transformer, and the input module is used for controlling a primary end of the transformer to generate alternating current according to the acquired input signal; the output module is used for receiving a voltage signal of the secondary end of the transformer and controlling the power tube to be switched on and off according to the received voltage signal. The input module includes: the control module is used for outputting a control signal according to the magnitude of the power supply voltage; and the current limiting resistance module is used for adjusting the magnitude of the current limiting resistance value in the input module according to the control signal so that the current limiting resistance value is increased along with the increase of the power supply voltage. When the power supply voltage is small, the current limiting resistance value is small so as to ensure that the driving current is large enough and realize effective sending and receiving of signals. With the increase of the power supply voltage, the current limiting resistance is increased, so that the driving current is reduced, and the power consumption of the chip is reduced.
Description
Technical Field
The disclosure relates to the field of electronic circuits, in particular to a power tube driving circuit and a power tube driving method.
Background
In an extra-high voltage power tube driving circuit, the problem that power domains of an input end and an output end are different exists, and an input ground is generally connected with a system ground and is 0V; the output ground is a floating ground and is connected with a power tube (for example, a source electrode of an IGBT), the minimum is 0V, and the maximum is several hundred volts or even more than one thousand volts. Therefore, it is necessary to perform isolation processing on the input and the output, such as isolation of the input and the output by using a transformer.
In the application of high integration, an input chip, an output chip and a transformer used for isolation are packaged together, in order to meet the requirement of small volume, the used chip-scale transformer is realized by manufacturing a coupling coil on a silicon chip, the inductance of the transformer is very small and is generally only in the order of tens of nano-farads. In order to transmit signals between the input and output stages, an alternating current signal is usually generated on the coil of the transmitting end of the transformer, and the signal coupling between the coils ensures that the receiving end receives the corresponding signal and processes and responds the signal.
To ensure that the secondary chip can correctly receive and recognize the corresponding signal, the current supplied to the transformer needs to be large enough, and if the current is small, the amplitude of the resonance on the transformer will decrease, and the secondary chip may not recognize the corresponding signal.
Disclosure of Invention
The purpose of the present disclosure is to provide a power tube driving circuit and a power tube driving method which are reliable and consume less power.
In order to achieve the above object, the present disclosure provides a power transistor driving circuit, which includes an input module, an output module, and a transformer, where the input module and the output module are connected through the transformer, and the input module is configured to control a primary end of the transformer to generate an alternating current according to an obtained input signal; the output module is used for receiving a voltage signal of the secondary end of the transformer and controlling the power tube to be switched on and off according to the received voltage signal.
Wherein the input module comprises:
the control module is used for outputting a control signal according to the magnitude of the power supply voltage;
and the current limiting resistance module is used for adjusting the magnitude of a current limiting resistance value in the input module according to the control signal so as to increase the current limiting resistance value along with the increase of the power supply voltage.
Optionally, the current-limiting resistance module includes a first preset resistance, n parallel resistances and n parallel switching tubes, the n parallel resistances correspond to the n parallel switching tubes one to one, each parallel resistance is connected in series with the corresponding parallel switching tube and then connected in parallel with the first preset resistance, and the parallel resistance is the current-limiting resistance in the input module.
The control signal comprises n sub-signals, the n parallel switch tubes correspondingly receive the n sub-signals one by one, and each parallel switch tube is used for controlling the on-off of the source electrode and the drain electrode according to the sub-signals received by the grid electrode.
Optionally, the current-limiting resistance module includes a first preset resistance, n series resistances and n series switching tubes, the n series resistances correspond to the n series switching tubes one by one, each series resistance is connected in parallel with the corresponding series switching tube, the first preset resistance is connected in series with the n series resistances, and the series resistances are the current-limiting resistances in the input module.
The control signal comprises n sub-signals, the n series-connected switching tubes receive the n sub-signals in a one-to-one correspondence mode, and each series-connected switching tube is used for controlling the on-off of the source electrode and the drain electrode according to the sub-signals received by the grid electrode.
Optionally, the current-limiting resistance module includes a parallel portion and a series portion, the parallel portion includes a first preset resistance, m mixed parallel resistances and m mixed parallel switching tubes, the m mixed parallel resistances and the m mixed parallel switching tubes are in one-to-one correspondence, and each mixed parallel resistance is connected in series with the corresponding mixed parallel switching tube and then connected in parallel with the first preset resistance.
The series part comprises (n-m) mixed series switch tubes and (n-m) mixed series resistors connected in series, the (n-m) mixed series resistors are in one-to-one correspondence with the (n-m) mixed series switch tubes, and each mixed series resistor is connected in parallel with the corresponding mixed series switch tube.
And the resistor formed by connecting the parallel part and the series part in series is a current-limiting resistor in the input module.
The control signal comprises n sub-signals, the m mixed parallel switch tubes and the (n-m) mixed series switch tubes correspondingly receive the n sub-signals one by one, and each mixed parallel switch tube and each mixed series switch tube are used for controlling the on-off of the source electrode and the drain electrode according to the sub-signals received by the grid electrode.
Optionally, the control module includes n voltage-dividing resistors and n voltage-dividing comparators, the n voltage-dividing resistors are connected in series between the power supply and the ground line, the n voltage-dividing resistors correspond to the n voltage-dividing comparators one to one, a predetermined reference voltage is input to a first input end of each voltage-dividing comparator, and a second input end of each voltage-dividing comparator is connected to the same side of the corresponding voltage-dividing resistor.
Wherein the n voltage division comparators output the n sub-signals respectively.
Optionally, the control module includes a first voltage-dividing resistor, a second voltage-dividing resistor, and n common voltage comparators, where the first voltage-dividing resistor and the second voltage-dividing resistor are connected in series between the power supply and the ground, a first input terminal of each common voltage comparator respectively inputs n different reference voltages, and a second input terminal of each common voltage comparator is connected between the first voltage-dividing resistor and the second voltage-dividing resistor.
Wherein the n common voltage comparators output the n sub-signals respectively.
Optionally, the control module includes a current source, a preset switching tube, and n signal generation submodules, where the n signal generation submodules output the n sub signals, and each signal generation submodule includes a first switching tube, a second switching tube, a voltage drop generation module, a second preset resistor, and a capacitor.
The source electrode of the preset switch tube, the source electrode of the first switch tube and the source electrode of the second switch tube are connected with the power supply, the drain electrode and the grid electrode of the preset switch tube are connected with the current source grounding wire, the grid electrode of the first switch tube is connected with the grid electrode of the preset switch tube, the drain electrode of the first switch tube is connected with the grid electrode of the second switch tube, the drain electrode of the first switch tube is connected with the voltage drop generation module grounding wire, the drain electrode of the second switch tube is connected with one end of the second preset resistor and one end of the capacitor, the other end of the second preset resistor and the other end of the capacitor are connected with the grounding wire, and the drain electrode of the second switch tube outputs the sub-signal.
Optionally, the voltage drop generating module includes a third switching tube and a fourth switching tube, a drain of the third switching tube is connected to a drain of the first switching tube, a diode connection method is used between the third switching tube and the fourth switching tube, and a source of the fourth switching tube is grounded.
Optionally, the third switching tube and the fourth switching tube are MOS tubes or triodes.
Optionally, the voltage drop generating module is a resistor or a diode.
The present disclosure also provides a power tube driving method applied to a power tube driving circuit, where the power tube driving circuit includes an input module, an output module, and a transformer, where the input module and the output module are connected through the transformer, and the method includes:
the input module controls the primary end of the transformer to generate alternating current according to the acquired input signal, wherein a control signal is output according to the magnitude of the power supply voltage; adjusting the size of a current-limiting resistance value in the input module according to the control signal so that the current-limiting resistance value is increased along with the increase of the power supply voltage;
the output module receives a voltage signal of the secondary end of the transformer and controls the power tube to be switched on and off according to the received voltage signal.
Through the technical scheme, the current-limiting resistance value in the input module of the power tube driving circuit is increased along with the increase of the power supply voltage, so that when the power supply voltage is lower, the current-limiting resistance value is lower, the driving current is ensured to be large enough, and the effective sending and receiving of signals are realized. With the increase of the power supply voltage, the current limiting resistance is increased, so that the driving current is reduced, and the power consumption of the chip is reduced.
Additional features and advantages of the disclosure will be set forth in the detailed description which follows.
Drawings
The accompanying drawings, which are included to provide a further understanding of the disclosure and are incorporated in and constitute a part of this specification, illustrate embodiments of the disclosure and together with the description serve to explain the disclosure without limiting the disclosure. In the drawings:
FIG. 1 is a schematic diagram of a basic principle of a power transistor driving circuit in the related art;
FIG. 2 is a schematic diagram of an input portion of a power transistor driving circuit in the related art;
FIG. 3 is a schematic diagram of a power tube driver circuit in accordance with an exemplary embodiment;
FIG. 4 is a schematic diagram of an input module of the power transistor driver circuit in accordance with an exemplary embodiment;
FIG. 5a is a schematic diagram of a current limiting resistance module of an exemplary embodiment;
FIG. 5b is a schematic diagram of a current limiting resistance module according to another exemplary embodiment;
FIG. 5c is a schematic diagram of a current limiting resistance module of yet another exemplary embodiment;
FIG. 6a is a schematic block diagram of a control module according to an exemplary embodiment;
FIG. 6b is a schematic block diagram of a control module according to another exemplary embodiment;
FIG. 6c is a schematic block diagram of a control module according to yet another exemplary embodiment;
7 a-7 c are schematic waveforms illustrating operation of the control module of FIG. 6 c;
fig. 8 is a flowchart of a power tube driving method according to an exemplary embodiment.
Detailed Description
The following detailed description of specific embodiments of the present disclosure is provided in connection with the accompanying drawings. It should be understood that the detailed description and specific examples, while indicating the present disclosure, are given by way of illustration and explanation only, not limitation.
Fig. 1 is a schematic diagram of a basic principle of a power transistor driving circuit in the related art. In the power transistor driving circuit 100 of fig. 1, there is a problem that the power domains of the input section 101 and the output section 102 are different, and the ground VSS1 of the input section 101 is connected to the system ground and is 0V; the ground VSS2 of the output portion 102 is a floating ground, and is connected to the source S of the power transistor IGBT, and has a minimum value of 0V, and a maximum value of several hundred volts or even more than one thousand volts. The output section 102 outputs a signal connected to the gate G of the IGBT, and the drain D of the IGBT may be connected to a power supply. An isolator 103 is provided between the input section 101 and the output section 102, and isolation processing is performed. The isolator 103 may be a transformer.
In high integration applications, the input part 101, the output part 102 and the transformer used as the isolator 103 are packaged together, and in order to meet the requirement of small size, the chip-scale transformer is implemented by making coupling coils on a silicon chip. The inductance of the transformer is very small, and in order to realize the transmission of signals between the input part 101 and the output part 102, the input part 101 generally transmits an alternating current signal to a coil at the transmitting end of the transformer, and the alternating current signal is transmitted to the output part 102 through signal coupling between the coils. To ensure that the output portion 102 can properly receive and recognize the signal, the current supplied to the transformer needs to be large enough, and if the current is small, the amplitude of the resonance on the transformer will decrease, and the output portion 102 may not recognize the signal.
Fig. 2 is a schematic diagram of a structure of an input portion of a power transistor driving circuit in the related art. The input part 101 receives an input signal, the input signal passes through an inverter Q1 and then is input into a NAND gate Q2, a signal generated by the frequency generation module is also input into a NAND gate Q2, the output of the NAND gate Q2 passes through a buffer Q3 and then is input into the gate of a first switch tube Q4, and the drain of the first switch tube Q4 is connected with a power supply (VDD) through a fixed resistor Rg. The source of the first switch transistor Q4 is connected to the drain of the second switch transistor Q5 and connected to one end of the isolator, the gate of the second switch transistor Q5 inputs the input signal, and the source of the second switch transistor Q5 is connected to the other end of the isolator and connected to ground. Above-mentioned fixed resistance Rg is used for carrying out the current-limiting, avoids the electric current through first switch tube Q4 too big, leads to the chip loss too big, causes local overheat even to burn out.
In the scheme of fig. 2, the current limiting resistor of the input part 101 of the power tube driving circuit is a fixed size, and the setting of the current limiting resistor value needs to consider the full operating voltage range. When the supply voltage is relatively low, the current limiting resistor must be small enough to ensure that the driving current is large enough to allow efficient signal transmission and reception. In this way, when the power voltage is high, the corresponding driving current is very large, which results in a significant increase in the power consumption of the chip. The inventors have conceived that the current limiting resistance value can be controlled to increase with an increase in the power supply voltage to reduce the power consumption of the chip.
Fig. 3 is a schematic diagram of a power transistor driving circuit according to an exemplary embodiment. As shown in fig. 3, the power tube driving circuit may include an input module 10, an output module 20, and a transformer 30, and the input module 10 and the output module 20 are connected through the transformer 30. The input module 10 is used for controlling the primary side of the transformer 30 to generate an alternating current according to the acquired input signal (e.g., PWM signal). The output module 20 is configured to receive a voltage signal at the secondary side of the transformer 30, and control the power tube to open or close according to the received voltage signal.
The input module 10 may include a control module 11 and a current limiting resistance module 12.
The control module 11 is configured to output a control signal according to a magnitude of the power voltage.
The current limiting resistance module 12 is used for adjusting the magnitude of the current limiting resistance value in the input module 10 according to the control signal, so that the current limiting resistance value is increased along with the increase of the power supply voltage.
Therefore, when the power supply voltage is small, the current limiting resistance value is small so as to ensure that the driving current is large enough and realize effective sending and receiving of signals. With the increase of the power supply voltage, the current limiting resistance is increased, so that the driving current is reduced, and the power consumption of the chip is reduced.
Fig. 4 is a schematic structural diagram of an input module of a power tube driving circuit according to an exemplary embodiment. As shown in fig. 4, on the basis of fig. 2, the current limiting resistor in the input module is replaced by a fixed resistor Rg as the control module 11 and the current limiting resistor module 12. The control module 11 is connected between the power supply and the ground, and the current-limiting resistance module 12 is connected between the power supply and the drain of the first switching tube Q4. The resistance between the R + and R-at the two ends of the current limiting resistance module 12 is an adjustable current limiting resistance, and the resistance value is controlled by the control module 11. The control module 11 controls the resistance value of the current limiting resistance module 12 according to the magnitude of the power supply voltage so that the resistance value (current limiting resistance value) thereof increases as the power supply voltage increases.
The current limiting resistance module 12 may be composed of resistors connected in series and/or in parallel, wherein the parallel connection is shown in fig. 5a, the series connection is shown in fig. 5b, and the series and parallel mixed manner is shown in fig. 5 c.
Fig. 5a is a schematic diagram of the structure of the current limiting resistance module 12 according to an exemplary embodiment. As shown in fig. 5a, the current limiting resistor module 12 may include a first preset resistor R0, n parallel resistors R11 to R1n, and n parallel switch tubes PM11 to PM1n, where the n parallel resistors correspond to the n parallel switch tubes one by one, each parallel resistor is connected in series with the corresponding parallel switch tube and then connected in parallel with the first preset resistor R0, and the resistor after parallel connection is a current limiting resistor in the input module 10.
That is, the first parallel resistor R11 is connected in series with the corresponding parallel switch PM11 and then connected in parallel with the first preset resistor R0, the second parallel resistor R12 is connected in series with the corresponding parallel switch PM12 and then connected in parallel with the first preset resistor R0, … …, and the nth parallel resistor R1n is connected in series with the corresponding parallel switch PM1n and then connected in parallel with the first preset resistor R0.
The parallel resistor is connected in series with the corresponding parallel switch tube, that is, the drain and the source of the parallel switch tube are connected in series with the parallel resistor as two ends, as shown in fig. 5 a. That is, the source of the parallel switch is connected to one end of the first preset resistor R0, and the drain of the parallel switch is connected to the other end of the first preset resistor R0 through the corresponding parallel resistor.
In this embodiment, the control signal includes n sub-signals, where n is an integer greater than or equal to 1. The n parallel switch tubes correspondingly receive the n sub-signals one by one, and each parallel switch tube is used for controlling the on-off of the source electrode and the drain electrode according to the sub-signals received by the grid electrode. The sub-signals received by the n parallel switch tubes PM 11-PM 1n are Ct 1-Ctn respectively.
In fig. 5a, the first preset resistor R0 is directly connected to the transformer driving circuit, and the n parallel resistors R11-R1 n are respectively controlled by the n parallel switching tubes PM 11-PM 1 n. In fig. 5a, a PMOS device is used as a switching tube, and when the sub-signal is "0", the corresponding parallel resistor is connected to the loop, so that the resistance value of the current-limiting resistor module 12 is reduced; when the sub-signal is "1", the corresponding parallel resistor breaks the loop, and the resistance value of the current-limiting resistor module 12 is increased.
Fig. 5b is a schematic structural diagram of the current limiting resistance module 12 of another exemplary embodiment. As shown in fig. 5b, the current limiting resistance module 12 may include a first pre-set resistor R0, n series resistors R21-R2 n, and n series switching tubes PM 21-PM 2 n. The n series resistors correspond to the n series switching tubes one by one, each series resistor is connected in parallel with the corresponding series switching tube, the first preset resistor R0 is connected in series with the n series resistors, and the resistors after series connection are current-limiting resistors in the input module 10.
That is, the first series resistor R21 is connected in parallel with the corresponding series switch PM21, the second series resistor R22 is connected in parallel with the corresponding series switch PM22, … …, and the nth series resistor R2n is connected in parallel with the corresponding series switch PM2 n.
The control signal comprises n sub-signals, n series-connected switching tubes receive the n sub-signals in a one-to-one correspondence mode, and each series-connected switching tube is used for controlling the on-off of the source electrode and the drain electrode according to the sub-signals received by the grid electrode.
In fig. 5b, the first pre-set resistor R0 is directly connected to the transformer driving circuit, and the n series resistors R21-R2 n are respectively controlled by the n series switching transistors PM 21-PM 2 n. In fig. 5b, a PMOS device is used as a switching tube, and when the sub-signal is "1", the corresponding series resistor is connected to the loop, so that the resistance value of the current-limiting resistor module 12 is increased; when the sub-signal is "0", the corresponding series resistor breaks the loop, and the resistance of the current-limiting resistor module 12 decreases.
In the control module 11, the magnitude of the power supply voltage may be determined by a comparator, and the sub-signals Ct1 to Ctn may be generated.
Fig. 5c is a schematic structural diagram of the current limiting resistance module 12 of yet another exemplary embodiment. As shown in fig. 5c, the current limiting resistance module 12 may include a parallel portion and a series portion. The parallel part can comprise a first pre-set resistor R0, m mixed parallel resistors R31-R3 m and m mixed parallel switch tubes PM 31-PM 3 m. The m mixed parallel resistors correspond to the m mixed parallel switch tubes one by one, and each mixed parallel resistor is connected with the corresponding mixed parallel switch tube in series and then is connected with the first preset resistor R0 in parallel.
The series part may comprise (n-m) hybrid series switching tubes PM3(m +1) -PM 3n and (n-m) hybrid series resistors R3(m +1) -R3 n connected in series. The (n-m) mixed series resistors correspond to the (n-m) mixed series switch tubes one by one, and each mixed series resistor is connected with the corresponding mixed series switch tube in parallel.
The resistor formed by connecting the parallel portion and the series portion in series is a current limiting resistor in the input module 10.
The control signal comprises n sub-signals, m mixed parallel switch tubes and (n-m) mixed series switch tubes receive the n sub-signals in a one-to-one correspondence mode, and each mixed parallel switch tube and each mixed series switch tube are used for controlling the on-off of a source electrode and a drain electrode according to the sub-signals received by the grid electrode. m is an integer less than n.
In fig. 5c, the first pre-set resistor R0 is directly connected to the transformer driving circuit, and the m hybrid parallel resistors R31-R3 m are respectively controlled by the m hybrid parallel switching tubes PM 31-PM 3 m. The (n-m) mixed series resistors R3(m +1) -R3 n are respectively controlled by (n-m) mixed series switching tubes PM3(m +1) -PM 3 n.
In fig. 5c, a PMOS device is also used as a switch tube, and when the sub-signal is "0", the corresponding hybrid parallel resistor or hybrid series resistor is connected to the loop, so that the resistance value of the current-limiting resistor module 12 is changed; when the sub-signal is "1", the corresponding hybrid parallel resistor or hybrid series resistor breaks the loop, and the resistance value of the current-limiting resistor module 12 is changed.
FIG. 6a is a schematic diagram of the structure of the control module 11 in an exemplary embodiment. As shown in FIG. 6a, the control module 11 may include n voltage-dividing resistors RA 1-RAn and n voltage-dividing comparators P11-P1 n. The n voltage-dividing resistors are connected in series between a power supply and a ground wire, and the n voltage-dividing resistors are in one-to-one correspondence with the n voltage-dividing comparators. The first input terminal (-) of each voltage-dividing comparator inputs a predetermined reference voltage VREF, and the second input terminal (+) of each voltage-dividing comparator is connected to the same side of the corresponding voltage-dividing resistor. Wherein, the n partial pressure comparators respectively output n sub-signals Ct 1-Ctn.
The voltage-dividing resistor is provided with two sides, one side is close to the power supply, and the other side is close to the ground wire. The second input end (+) of each voltage division comparator is connected to one side of the corresponding voltage division resistor close to the power supply, or is connected to one side of the corresponding voltage division resistor close to the ground wire.
In fig. 6a, each of the voltage dividing comparators has a first input (-) connected to the reference voltage VREF and a second input (+) connected to the resistive voltage dividing sample terminal of the power supply. The n voltage-dividing resistors are connected in series to form a voltage-dividing circuit. Taking the generation process of the control signal Ct1 in fig. 6a as an example, when the power supply voltage VDD is high enough and VREF < VF1, the sub-signal Ct1 generated at this time is "1", and is output to the current-limiting resistance module 12, and the parallel resistor corresponding to the sub-signal Ct1 in fig. 5a is in an off state;
along with the reduction of the power supply voltage VDD, when VF1 is less than VREF, the generated sub-signal Ct1 is "0" and is output to the current-limiting resistance module 12, and the parallel resistance corresponding to the sub-signal Ct1 in fig. 5a is in an access state, which reduces the equivalent impedance on the driving loop, that is, reduces the resistance value of the current-limiting resistance module 12, and further increases the transformer driving current that can be provided under the corresponding power supply voltage.
The generation principle of the sub-signals Ct 2-Ctn is similar to that of Ct1, and the turning points of the voltage division comparators P11-P1 n can be realized by adjusting the input reference or adjusting the voltage division resistance ratio of the power supply. In fig. 6a, multiple comparators correspond to the same reference voltage and different sampling inputs.
Fig. 6b is a schematic structural diagram of the control module 11 of another exemplary embodiment. In fig. 6b, multiple comparators correspond to the same sample input and different reference voltages. As shown in fig. 6b, the control module 11 includes a first voltage-dividing resistor RB1, a second voltage-dividing resistor RB2, and n common voltage comparators P21 to P2 n. The first voltage-dividing resistor and the second voltage-dividing resistor are connected in series between a power supply and a ground wire to form a voltage-dividing circuit. The first input end (-) of each common voltage comparator respectively inputs n different reference voltages VREF 1-VREFn, and the second input end (+) of each common voltage comparator is connected between the first voltage dividing resistor and the second voltage dividing resistor. The voltage dividing resistor between the first voltage dividing resistor and the second voltage dividing resistor is VF. Wherein, the n common voltage comparators respectively output n sub-signals Ct 1-Ctn.
FIG. 6c is a schematic diagram of a control module according to yet another exemplary embodiment. As shown in fig. 6C, the control module 11 includes a current source I0, a preset switching tube PM0, and n signal generation submodules 111 to 11n, where the n signal generation submodules output n sub-signals Ct1 to Ctn, respectively, and each signal generation submodule includes a first switching tube PMa, a second switching tube PMb, a voltage drop generation module, a second preset resistor RC, and a capacitor C0.
The source electrode of the preset switching tube PM0, the source electrode of the first switching tube PMa and the source electrode of the second switching tube PMb are connected with a power supply, the drain electrode and the grid electrode of the preset switching tube PM0 are connected with a current source grounding wire, the grid electrode of the first switching tube PMa is connected with the grid electrode of the preset switching tube PM0, the drain electrode of the first switching tube PMa is connected with the grid electrode of the second switching tube PMb, the drain electrode of the first switching tube PMa is connected with a module grounding wire through a voltage drop generation module, the drain electrode of the second switching tube PMb is connected with one end of the second preset resistor RC and one end of the capacitor C0, the other end of the second preset resistor RC and the other end of the capacitor C0 are connected with a grounding wire, and the drain electrode of the second switching tube PMb outputs sub-signals.
The voltage drop generating module in fig. 6c includes a third switching tube NM1 and a fourth switching tube NM 2. The drain of the third switching tube NM1 is connected to the drain of the first switching tube, a diode is connected between the third switching tube NM1 and the fourth switching tube NM2, and the source of the fourth switching tube NM2 is grounded.
The third switch tube NM1 and the fourth switch tube NM2 may be MOS transistors or triodes. The third switching tube NM1 and the fourth switching tube NM2 in fig. 6c are N-type MOS transistors.
Fig. 7 a-7 c are schematic waveforms illustrating the operation of the control module 11 of fig. 6 c. The current source I0 generates a voltage drop across the third switch NM1 and the fourth switch NM2, the voltage is VNET0, when the power supply voltage VDD is high enough to keep I0 constant, VNET0 will also be fixed, and as the power supply voltage VDD decreases, when it approaches VNET0, the current I1 will not be kept and decrease, and accordingly, VNET0 will also decrease and substantially follow the power supply voltage VDD, as shown in fig. 7 a.
The difference V1 between the power voltage VDD and VNET0 is VDD-VNET0, the magnitude of V1 controls the conduction of the second switching tube PMb, and further controls the magnitude of the output current I2 of the second switching tube PMb, and the magnitude of the current I2 is mainly determined by the device size (current) of the second switching tube PMb and the magnitude of V1, and is in a direct proportion relationship. Given the size of the second switching transistor PMb, there is I2 ═ K × V1, where K is the relevant current generation coefficient, and is related to the operating state of the device. The maximum value of I2 is limited by the power voltage VDD/R1, and R1 is the resistance of the second predetermined resistor RC.
That is, when K × V1> VDD/R1, I2 is VDD/R1; when K × V1 ═ VDD/R1, I2 ═ K × V1. The output signal Ct1 of the control module 11 is the voltage drop I2 × R1 generated by I2 across the second pre-set resistor RC, as shown in fig. 7b and 7 c.
When the power supply voltage is high enough, the Ct1 signal outputted at this time will approach the power supply voltage VDD, the corresponding switch tube in the current-limiting resistance module 12 is turned off, and the corresponding parallel resistor in fig. 5a is disconnected from the driving circuit.
With the gradual decrease of the power supply voltage VDD, V1 will decrease, and when K × V1 is less than or equal to VDD/R1, the current I2 will decrease gradually from VDD/R1, and further, the Ct1 voltage will also decrease gradually from the power supply voltage VDD, and turn on the corresponding switch tube in the current limiting resistor module 12 gradually until it is completely turned on, and the resistor in fig. 5a will gradually connect into the driving loop, so as to improve the power supply capability of the driving loop under the current power supply voltage. When the power supply voltage VDD decreases to turn off the second switching tube PMb, I2 is 0, and the Ct1 output is pulled down to "0" by R1, as shown in fig. 7 c.
The threshold of the access control signal (sub-signals Ct 1-Ctn) of the resistor in the current limiting resistor module 12 is mainly determined by the size of the current source I0 and the devices of the third switching tube NM1 and the fourth switching tube NM2, wherein the current source I0 is controlled by the size of the first switching tube PMa.
Besides the MOS transistor, the voltage drop generating module may also be a resistor or a diode.
The disclosure also provides a power tube driving method applied to the power tube driving circuit. The power tube driving circuit comprises an input module 10, an output module 20 and a transformer 30, wherein the input module 10 and the output module 20 are connected through the transformer 30. Fig. 8 is a flowchart of a power transistor driving method according to an exemplary embodiment. As shown in fig. 8, the method may include:
in step S101, the input module 10 controls the primary terminal of the transformer 30 to generate an alternating current according to the acquired input signal. Wherein, a control signal is output according to the magnitude of the power voltage, and the magnitude of the current-limiting resistance value in the input module 10 is adjusted according to the control signal, so that the current-limiting resistance value increases with the increase of the power voltage.
In step S102, the output module 20 receives the voltage signal of the secondary side of the transformer 30, and controls the power tube to be turned on or off according to the received voltage signal.
Through the technical scheme, the current-limiting resistance value in the input module of the power tube driving circuit is increased along with the increase of the power supply voltage, so that when the power supply voltage is lower, the current-limiting resistance value is lower, the driving current is ensured to be large enough, and the effective sending and receiving of signals are realized. With the increase of the power supply voltage, the current limiting resistance is increased, so that the driving current is reduced, and the power consumption of the chip is reduced.
The preferred embodiments of the present disclosure are described in detail with reference to the accompanying drawings, however, the present disclosure is not limited to the specific details of the above embodiments, and various simple modifications may be made to the technical solution of the present disclosure within the technical idea of the present disclosure, and these simple modifications all belong to the protection scope of the present disclosure.
It should be noted that the various features described in the above embodiments may be combined in any suitable manner without departing from the scope of the invention. In order to avoid unnecessary repetition, various possible combinations will not be separately described in this disclosure.
In addition, any combination of various embodiments of the present disclosure may be made, and the same should be considered as the disclosure of the present disclosure, as long as it does not depart from the spirit of the present disclosure.
Claims (11)
1. A power tube driving circuit, characterized in that the power tube driving circuit comprises an input module (10), an output module (20) and a transformer (30), the input module (10) and the output module (20) are connected through the transformer (30), the input module (10) is used for controlling a primary side of the transformer (30) to generate an alternating current according to an acquired input signal; the output module (20) is used for receiving a voltage signal of the secondary end of the transformer (30) and controlling the on-off of the power tube according to the received voltage signal,
wherein the input module (10) comprises:
the control module (11) is used for outputting a control signal according to the magnitude of the power supply voltage;
and the current limiting resistance module (12) is used for adjusting the magnitude of a current limiting resistance value in the input module (10) according to the control signal so that the current limiting resistance value is increased along with the increase of the power supply voltage.
2. The power tube driving circuit according to claim 1, wherein the current limiting resistor module (12) comprises a first preset resistor (R0), n parallel resistors (R11-R1 n) and n parallel switch tubes (PM 11-PM 1n), the n parallel resistors and the n parallel switch tubes are in one-to-one correspondence, each parallel resistor and the corresponding parallel switch tube are connected in series and then connected in parallel with the first preset resistor (R0), and the resistors after being connected in parallel are current limiting resistors in the input module (10),
the control signal comprises n sub-signals, the n parallel switch tubes correspondingly receive the n sub-signals one by one, and each parallel switch tube is used for controlling the on-off of the source electrode and the drain electrode according to the sub-signals received by the grid electrode.
3. The power tube driving circuit according to claim 1, wherein the current limiting resistor module (12) comprises a first preset resistor (R0), n series resistors (R21-R2 n) and n series switching tubes (PM 21-PM 2n), the n series resistors and the n series switching tubes are in one-to-one correspondence, each series resistor is connected with the corresponding series switching tube in parallel, the first preset resistor and the n series resistors are connected in series, and the series resistors are current limiting resistors in the input module (10),
the control signal comprises n sub-signals, the n series-connected switching tubes receive the n sub-signals in a one-to-one correspondence mode, and each series-connected switching tube is used for controlling the on-off of the source electrode and the drain electrode according to the sub-signals received by the grid electrode.
4. The power tube driving circuit according to claim 1, wherein the current limiting resistance module (12) comprises a parallel part and a series part, the parallel part comprises a first preset resistance (R0), m mixed parallel resistances (R31-R3 m) and m mixed parallel switch tubes (PM 31-PM 3m), the m mixed parallel resistances and the m mixed parallel switch tubes are in one-to-one correspondence, each mixed parallel resistance and the corresponding mixed parallel switch tube are connected in series and then connected in parallel with the first preset resistance (R0),
the series part comprises (n-m) mixed series switch tubes (PM3(m +1) -PM 3n) and (n-m) mixed series resistors (R3(m +1) -R3 n) connected in series, the (n-m) mixed series resistors are in one-to-one correspondence with the (n-m) mixed series switch tubes, each mixed series resistor is connected with the corresponding mixed series switch tube in parallel,
the resistor formed by connecting the parallel part and the series part in series is a current-limiting resistor in the input module (10),
the control signal comprises n sub-signals, the m mixed parallel switch tubes and the (n-m) mixed series switch tubes correspondingly receive the n sub-signals one by one, and each mixed parallel switch tube and each mixed series switch tube are used for controlling the on-off of the source electrode and the drain electrode according to the sub-signals received by the grid electrode.
5. The power tube driving circuit according to any of the claims 2-4, wherein the control module (11) comprises n voltage dividing resistors (RA 1-RAn) and n voltage dividing comparators (P11-P1 n), the n voltage dividing resistors are connected in series between the power supply and the ground, the n voltage dividing resistors and the n voltage dividing comparators are in one-to-one correspondence, a first input terminal of each voltage dividing comparator inputs a predetermined reference Voltage (VREF), a second input terminal of each voltage dividing comparator is connected to the same side of the corresponding voltage dividing resistor,
wherein the n voltage division comparators output the n sub-signals respectively.
6. The power tube driving circuit according to any of the claims 2-4, wherein the control module (11) comprises a first voltage dividing resistor (RB1), a second voltage dividing resistor (RB2), n common voltage comparators (P21-P2 n), the first voltage dividing resistor and the second voltage dividing resistor are connected in series between the power supply and the ground, the first input terminal of each common voltage comparator respectively inputs n different reference voltages (VREF 1-VREFn), the second input terminal of each common voltage comparator is connected between the first voltage dividing resistor and the second voltage dividing resistor,
wherein the n common voltage comparators output the n sub-signals respectively.
7. A power tube driving circuit according to any one of claims 2-4, characterized in that the control module (11) comprises a current source (I0), a pre-set switching tube (PM0) and n signal generating sub-modules (111-11 n) outputting the n sub-signals respectively, each signal generating sub-module comprising a first switching tube (PMa), a second switching tube (PMb), a voltage drop generating module, a second pre-set Resistor (RC) and a capacitor (C0),
the source electrode of the preset switching tube, the source electrode of the first switching tube and the source electrode of the second switching tube are connected with a power supply, the drain electrode and the grid electrode of the preset switching tube pass through the current source grounding wire, the grid electrode of the first switching tube is connected with the grid electrode of the preset switching tube, the drain electrode of the first switching tube is connected with the grid electrode of the second switching tube, the drain electrode of the first switching tube passes through the voltage drop generation module grounding wire, the drain electrode of the second switching tube is connected with one end of the second preset resistor and one end of the capacitor, the other end of the second preset resistor and the other end of the capacitor are connected with the grounding wire, and the drain electrode of the second switching tube outputs the sub-signal.
8. The power tube driving circuit according to claim 7, wherein the voltage drop generating module comprises a third switching tube (NM1) and a fourth switching tube (NM2), a drain of the third switching tube is connected to a drain of the first switching tube, a diode is connected between the third switching tube and the fourth switching tube, and a source of the fourth switching tube is connected to a ground line.
9. The power tube driving circuit according to claim 8, wherein the third switching tube and the fourth switching tube are MOS tubes or triodes.
10. The power tube driving circuit according to claim 7, wherein the voltage drop generating module is a resistor or a diode.
11. A power tube driving method applied to a power tube driving circuit, wherein the power tube driving circuit comprises an input module (10), an output module (20) and a transformer (30), the input module (10) and the output module (20) are connected through the transformer (30), and the method comprises:
the input module (10) controls the primary end of the transformer (30) to generate alternating current according to the acquired input signal, wherein a control signal is output according to the magnitude of the power supply voltage, and the magnitude of a current limiting resistance value in the input module (10) is adjusted according to the control signal, so that the current limiting resistance value is increased along with the increase of the power supply voltage;
the output module (20) receives a voltage signal of a secondary end of the transformer (30) and controls the power tube to be switched on and off according to the received voltage signal.
Priority Applications (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202110335392.7A CN115133917A (en) | 2021-03-29 | 2021-03-29 | Power tube driving circuit and power tube driving method |
| PCT/CN2022/081995 WO2022206450A1 (en) | 2021-03-29 | 2022-03-21 | Power transistor driver circuit and power transistor driving method |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202110335392.7A CN115133917A (en) | 2021-03-29 | 2021-03-29 | Power tube driving circuit and power tube driving method |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN115133917A true CN115133917A (en) | 2022-09-30 |
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Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202110335392.7A Pending CN115133917A (en) | 2021-03-29 | 2021-03-29 | Power tube driving circuit and power tube driving method |
Country Status (2)
| Country | Link |
|---|---|
| CN (1) | CN115133917A (en) |
| WO (1) | WO2022206450A1 (en) |
Family Cites Families (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP3494154B2 (en) * | 2001-03-12 | 2004-02-03 | 日産自動車株式会社 | Power transistors for driving power transistors |
| US9866123B2 (en) * | 2013-10-31 | 2018-01-09 | Dialog Semiconductor Inc. | Power converter with dynamic preload |
| CN104467372B (en) * | 2014-12-18 | 2017-02-22 | 矽力杰半导体技术(杭州)有限公司 | Switch power controller and control method thereof |
| CN111446847B (en) * | 2020-05-18 | 2024-08-02 | 华源智信半导体(深圳)有限公司 | Power converter, switching tube driving method and power system |
-
2021
- 2021-03-29 CN CN202110335392.7A patent/CN115133917A/en active Pending
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2022
- 2022-03-21 WO PCT/CN2022/081995 patent/WO2022206450A1/en not_active Ceased
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| WO2022206450A1 (en) | 2022-10-06 |
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