CN112366934B - Single-stage power factor correction control circuit and switching power supply - Google Patents
Single-stage power factor correction control circuit and switching power supply Download PDFInfo
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- CN112366934B CN112366934B CN202011204597.3A CN202011204597A CN112366934B CN 112366934 B CN112366934 B CN 112366934B CN 202011204597 A CN202011204597 A CN 202011204597A CN 112366934 B CN112366934 B CN 112366934B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
- H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
- H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
- H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
- H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
- H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
- H02M7/12—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
- H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
- H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
- H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
- H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
- H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
- H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/4815—Resonant converters
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Rectifiers (AREA)
- Dc-Dc Converters (AREA)
Abstract
本发明公开了一种单级功率因数校正控制电路及开关电源，该单级功率因素校正控制电路包括电网输入Vin、整流桥DB1、电容C1、电容C2、开关管S1、开关管S2、开关管S3、二极管D1、电感L1、变压器T1、第一输出整流电路、输出电容Co、功率因素校正控制电路及谐振控制驱动电路。有益效果：本发明提供一种单级功率因素校正控制电路，在较宽的输入电网电压范围内，实现功率因数校正，降低电流谐波失真，也能限制和稳定母线电容电压，避免器件过应力。
The present invention discloses a single-stage power factor correction control circuit and a switching power supply, wherein the single-stage power factor correction control circuit comprises a power grid input Vin, a rectifier bridge DB1, a capacitor C1, a capacitor C2, a switch tube S1, a switch tube S2, a switch tube S3, a diode D1, an inductor L1, a transformer T1, a first output rectifier circuit, an output capacitor Co, a power factor correction control circuit and a resonance control drive circuit. Beneficial effects: The present invention provides a single-stage power factor correction control circuit, which realizes power factor correction and reduces current harmonic distortion within a wider input power grid voltage range, and can also limit and stabilize bus capacitor voltage and avoid device overstress.
Description
Technical Field
The invention relates to the field of circuits and switching power supplies, in particular to a single-stage power factor correction control circuit and a switching power supply.
Background
In the power field, high power density, high efficiency and low cost drive power supplies are more competitive. The resonant circuit is typically selected by the driving power supply to achieve high power density and high efficiency. The resonance circuit can realize zero-voltage on of two or more switching tubes on the primary side and zero-current off of a rectifier diode on the secondary side, can reduce the switching loss of a power supply and improve the efficiency and the power density of the power converter. Meanwhile, in order to improve the power factor, a primary active PFC power factor correction circuit is often added in front of the resonant circuit, but this results in complicated circuit and high cost.
For this reason, in the prior art, a charge pump circuit replaces a PFC circuit, so that a single-stage resonant circuit meets the power factor requirement. However, a resonant circuit with a charge pump has the problem that when the circuit is in an operating condition in which the amplitude of the input voltage varies within a certain range, the voltage on the bus capacitor increases as the amplitude of the input voltage increases and the energy required by the resonant main circuit is unchanged, or when the output power of the resonant main circuit varies within a certain range (i.e. the power required by the resonant main circuit varies within a certain range), the output power decreases and the voltage on the bus capacitor increases as the input voltage is unchanged. If the voltage on the bus capacitor is at a higher amplitude level, the relevant devices of the subsequent resonant main circuit need to withstand higher voltage pressures. Therefore, when designing a circuit, these devices of the resonant main circuit need to select withstand voltage performance according to the bus capacitance voltage of the highest magnitude. Devices with high withstand voltage are expensive, and for circuits that operate for long periods of time at low magnitude bus capacitor voltages, and occasionally at high magnitude bus capacitor voltages, selecting a device with high withstand voltage is wasteful and must be selected, otherwise, at high magnitude bus capacitor voltages, the device may be damaged due to withstand voltage problems.
Meanwhile, the charge pump PFC is difficult to realize ideal power factor correction in a wider input and load range as a passive measure, and the power factor and harmonic effect are not ideal.
In view of this, how to limit the voltage stability of the bus capacitor to a certain voltage value, avoid the voltage pressure caused to the device due to the over-high voltage of the bus capacitor, and realize better power factor correction in a wider input and load range, which has become a technical problem to be solved by those skilled in the art.
For the problems in the related art, no effective solution has been proposed at present.
Disclosure of Invention
Aiming at the problems in the related art, the invention provides a single-stage power factor correction control circuit and a switching power supply, so as to overcome the technical problems in the prior art.
For this purpose, the invention adopts the following specific technical scheme:
According to an aspect of the present invention, there is provided a single-stage power factor correction control circuit, including a grid input Vin, a rectifier bridge DB1, a capacitor C2, a switching tube S1, a switching tube S2, a switching tube S3, a diode D1, an inductance L1, a transformer T1, a first output rectifier circuit, an output capacitor Co, a power factor correction control circuit, and a resonance control driving circuit;
The power grid input Vin is connected with a first end and a third end of the rectifier bridge DB1, a second end of the rectifier bridge DB1 is sequentially connected with a positive electrode of the capacitor C1 and a first end of the switching tube S1, a second end of the switching tube S1 is sequentially connected with one end of the inductor L1 and a first end of the switching tube S2, the other end of the inductor L1 is connected with a first input end of the transformer T1, a second input end of the transformer T1 is connected with one end of the capacitor C2, an output end of the transformer T1 is connected with the first output rectifier circuit in parallel, the first output rectifier circuit is connected with the output capacitor Co in parallel, the other end of the capacitor C2 is sequentially connected with a first end of the switching tube S3, a negative electrode of the diode D1 and a third end of the rectifier bridge DB1, a positive electrode of the diode D1 is sequentially connected with a negative electrode of the capacitor C1, a second end of the switching tube S3 and a second end of the switching tube S2 are connected with the third end of the switching tube S2 in parallel, and the driving circuit is connected with the third end of the switching tube S2 is connected with the driving circuit;
When the L1 inductance current flows in the positive half cycle, the conduction time of the switch tube S3 is controlled, the current of the capacitor C1 can be controlled through the rectifier bridge DB1 and the input power grid Vin, the longer the conduction time of the switch tube S3 is, the smaller the current of the capacitor C1 is, and conversely, the shorter the conduction time of the switch tube S3 is, the larger the current of the capacitor C1 is, when the conduction time of the switch tube S3 is at a certain value, the charging current and the discharging current of the capacitor C1 are equal, and the voltage of the capacitor C1 is at a steady state;
According to the input power grid voltage, the on time or the on duty ratio of the switching tube S3 is controlled and modulated, so that the average value of the current flowing through the rectifier bridge DB1 and the power grid tracks the input power grid voltage in the power frequency period, and the power factor correction function can be realized.
Further, the capacitor C1 is a polar capacitor.
Further, the output capacitor Co is a polar capacitor.
Further, when the current of the inductor L1 flows from right to left and the negative half cycle, the diode D1 is turned on, the rectifier bridge DB1 is turned off, and the current does not pass through the input power grid Vin.
Further, when the current of the inductor L1 flows from left to right and in the positive half cycle, if the switching tube S3 is turned on, the rectifier bridge DB1 is turned off, and the current does not pass through the input power grid Vin.
Further, when the current of the inductor L1 flows from left to right and in the positive half cycle, if the switching tube S3 is turned off, the rectifier bridge DB1 is turned on, and the current passes through the input power grid Vin.
Further, the resonance control driving circuit provides energy for the output capacitor Co and the load through the transformer T1 and the first output rectifying circuit.
Further, the resonance control driving circuit adopts frequency feedback control of output voltage or output current.
According to another aspect of the present invention, there is provided a switching power supply composed of the above single-stage power factor correction control circuit.
The beneficial effects of the invention are as follows:
(1) The invention provides a single-stage power factor correction control circuit, which realizes power factor correction in a wider input power grid voltage range, reduces current harmonic distortion, can limit and stabilize bus capacitor voltage, and avoids overstress of devices.
(2) According to the single-stage power factor correction control circuit, the voltage of the capacitor C1 is limited and stabilized by controlling the on time of the switch S3, so that overstress of a circuit device is prevented. Meanwhile, the input grid current is sampled, and the capacitance peak voltage represents the current average value through capacitance integration. By adopting a peak control mode and controlling the conduction time of the switch S3, the input current tracks the input grid voltage, and the power factor correction function is realized. The single-stage power factor correction circuit is simple in circuit and convenient to control. The circuit cost is lower compared to a two-stage circuit. Compared with a passive charge pump PFC, the bus capacity voltage and the power factor can be well considered, and the power pump PFC can be suitable for a wider input and output load range.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings that are needed in the embodiments will be briefly described below, and it is obvious that the drawings in the following description are only some embodiments of the present invention, and other drawings may be obtained according to these drawings without inventive effort for a person skilled in the art.
FIG. 1 is a schematic diagram of a first embodiment according to the present invention;
FIG. 2 is a voltage waveform diagram according to a first embodiment of the present invention;
FIG. 3 is a partial schematic view of a first embodiment according to the present invention;
FIG. 4 is a schematic diagram of a second embodiment according to the present invention;
FIG. 5 is a voltage waveform diagram according to a second embodiment of the present invention;
fig. 6 is a schematic diagram of the pfc control circuit of fig. 4.
Detailed Description
For the purpose of further illustrating the various embodiments, the present invention provides the accompanying drawings, which are a part of the disclosure of the present invention, and which are mainly used to illustrate the embodiments and, together with the description, serve to explain the principles of the embodiments, and with reference to these descriptions, one skilled in the art will recognize other possible implementations and advantages of the present invention, wherein elements are not drawn to scale, and like reference numerals are generally used to designate like elements.
According to an embodiment of the invention, a single-stage power factor correction control circuit and a switching power supply are provided.
Example 1
The present invention will be further described with reference to the accompanying drawings and the specific embodiments, as shown in fig. 1, a single-stage power factor correction control circuit according to an embodiment of the present invention includes a power grid input Vin, a rectifier bridge DB1, a capacitor C2, a switching tube S1, a switching tube S2, a switching tube S3, a diode D1, an inductor L1, a transformer T1, a first output rectifier circuit, an output capacitor Co, a power factor correction control circuit and a resonance control driving circuit;
The power grid input Vin is connected with a first end and a third end of the rectifier bridge DB1, a second end of the rectifier bridge DB1 is sequentially connected with a positive electrode of the capacitor C1 and a first end of the switch tube S1, a second end of the switch tube S1 is sequentially connected with one end of the inductor L1 and a first end of the switch tube S2, the other end of the inductor L1 is connected with a first input end of the transformer T1, a second input end of the transformer T1 is connected with one end of the capacitor C2, an output end of the transformer T1 is connected with the first output rectifier circuit in parallel, the first output rectifier circuit is connected with the output capacitor Co in parallel, the other end of the capacitor C2 is sequentially connected with a first end of the switch tube S3, a negative electrode of the diode D1 and a third end of the rectifier bridge DB1, a positive electrode of the diode D1 is sequentially connected with a negative electrode of the capacitor C1, a second end of the switch tube S3 and a second end of the switch tube S2 are connected with the third end of the switch tube S2 in parallel, and the third end of the switch tube S2 is connected with the drive tube S is connected with the third end of the drive tube S2.
In one embodiment, for the capacitor C1, the capacitor C1 is a polar capacitor.
In one embodiment, for the output capacitor Co, the output capacitor Co is a polar capacitor.
In one embodiment, when the current of the inductor L1 flows from right to left for a negative half cycle, the diode D1 is turned on, the rectifier bridge DB1 is turned off, and the current does not pass through the input grid Vin.
In one embodiment, when the current of the inductor L1 flows from left to right in the positive half cycle, if the switching tube S3 is turned on, the rectifier bridge DB1 is turned off, and the current does not pass through the input power grid Vin.
In one embodiment, when the current of the inductor L1 flows from left to right and in a positive half cycle, if the switching tube S3 is turned off, the rectifier bridge DB1 is turned on, and the current passes through the input power grid Vin.
In one embodiment, the resonant control driving circuit provides energy to the output capacitor Co and the load through the transformer T1, the first output rectifying circuit.
In one embodiment, the resonant control driving circuit adopts frequency feedback control of the output voltage or the output current, the control mode is similar to that of a common series resonance or series-parallel resonance circuit, the switching tube S1 and the switching tube S2 are symmetrically and complementarily driven, and the set output voltage Vo or the set output current Io is obtained through frequency control.
The invention also provides a switching power supply which consists of the single-stage power factor correction control circuit.
In one embodiment, when the switching tube S3 is always turned on, the input power grid Vin, the rectifier bridge DB1 and the capacitor C1 form an uncontrolled rectifier circuit, no power factor correction function is achieved, the working voltage of the capacitor C1 is the lowest, the power grid current harmonic is also large, and when the switching tube S3 is always turned off, the positive half-cycle resonant current of the L1 inductor is all input to the power grid Vin through the rectifier bridge DB1 to charge the capacitor C1. The current flowing through the switching tube S1 is necessarily smaller than the positive half-cycle current of the inductor L1, so that the charging current is always larger than the discharging current, and the voltage of the capacitor C1 is always increased until the device is damaged. As shown in fig. 2 and 3, controlling the on time of the switching tube S3 can limit and stabilize the voltage of the capacitor C1. When the inductance current of the L1 flows in the positive half cycle, the conduction time of the switching tube S3 is controlled, so that the current for charging the capacitor C1 through the rectifier bridge DB1 and the input power grid Vin can be controlled, the longer the conduction time of the switching tube S3 is, the smaller the current for charging the capacitor C1 is, otherwise, the shorter the conduction time of the switching tube S3 is, the larger the current for charging the capacitor C1 is. When the on time of the switching tube S3 is at a certain value, the charging and discharging currents of the capacitor C1 are equal, and the voltage of the capacitor C1 is in a steady state. Therefore, the on time of the switch tube S3 is controlled, so that the voltage of the capacitor C1 can be limited and stabilized, and overstress of a circuit device is avoided.
In one embodiment, according to the input power grid voltage, the on time or the on duty ratio of the switching tube S3 is controlled and modulated, so that the average value of the current flowing through the rectifier bridge DB1 and the power grid is tracked in the power frequency period, the power factor correction function can be realized, the input power factor is improved, and the current harmonic is reduced.
In one embodiment, the power factor correction control circuit performs feedback control to stabilize the voltage of the bus capacitor C1, thereby realizing a power factor correction function.
Example two
As shown in fig. 4, the single-stage power factor correction control circuit according to the embodiment of the invention includes a power grid input Vin, a rectifier bridge DB1, a capacitor C2, a switching tube S1, a switching tube S2, a switching tube S3, a diode D1, an inductor L1, a transformer T1, a first output rectifier circuit, an output capacitor Co, a power factor correction control circuit, a resonance control driving circuit, a second output rectifier circuit, a current transformer CT1, a capacitor C3 and a switching tube S4;
The second end of the rectifier bridge DB1 is sequentially connected with the positive electrode of the capacitor C1 and the first end of the switch tube S1, the second end of the switch tube S1 is sequentially connected with one end of the inductor L1 and the first end of the switch tube S2, the other end of the inductor L1 is sequentially connected with the first input end of the transformer T1, the second input end of the transformer T1 is connected with one end of the capacitor C2, the output end of the transformer T1 is connected with the first output rectifier circuit in parallel, the first output rectifier circuit is connected with the output capacitor Co in parallel, the other end of the capacitor C2 is sequentially connected with the Vds_s3 end of the power factor correction control circuit, the first end of the switch tube S3, the negative electrode of the diode D1 and the second input end of the current transformer CT1, the positive electrode of the diode D1 is sequentially connected with the first input end of the capacitor C1, the second input end of the switch tube S3 and the switch tube S3 are sequentially connected with the first end of the switch tube C1, the second end of the switch tube S3 is connected with the first end of the switch tube C3 and the switch tube C2 in parallel, the three ends of the switch tube C1 is connected with the three ends of the switch tube C3 and the switch tube C3 in parallel, the three ends of the switch tube C1 is connected with the three ends of the switch tube C2, the three ends of the switch tube C2 is connected with the three ends of the switch tube C1 and the three voltage is connected with the three ends of the three voltage transformer, the three voltage is connected with the three voltage transformer, and the three voltage is connected with the three voltage bridge, and the voltage bridge is connected to the voltage bridge and the voltage, the positive electrode of the capacitor C3 is sequentially connected with the Vc end of the power factor correction control circuit and the second end of the switching tube S4, the third end of the switching tube S4 is connected with the Vg_s4 end of the power factor correction control circuit, and the vin_rec end of the power factor correction control circuit is connected with the second output rectifying circuit;
wherein, the capacitor C3 is a polar capacitor.
In one embodiment, as shown in fig. 4, the input grid current is sampled by a current transformer CT1, charge integration is performed by a capacitor C3, and each time the switching tube S3 is turned on, the switching tube S4 is turned on to release and reset the voltage across the capacitor C3 to zero. When the capacitance C1 is sufficiently large, it can be approximately considered that the resonant circuit switching frequency is substantially the same throughout the power frequency period. As is known from i×t=c×v, the peak value of the capacitor C3 is proportional to the average current flowing through the input grid during the switching period, and the magnitude of the peak value is indicative of the average value of the input current during the switching period. The average value of the input current can be modulated and controlled by modulating the on-duty ratio of the switching tube S3 by peak comparison control.
In one embodiment, as shown in fig. 6, an operational amplifier negative feedback circuit is used to realize the voltage control of the bus capacitor C1, and PI integral control is used as loop compensation;
In one embodiment, as shown in fig. 5 and 6, the negative feedback output Vcomp of the operational amplifier and the steamed bread wave voltage of the input voltage Vin are used as the peak comparison reference of the voltage Vc of the capacitor C3 through a multiplier, when the Vc rises to the reference, the switching tube S3 is turned on, and the input current is indirectly controlled to follow the input voltage through the peak control of the charge integration following input power grid, so that the power factor correction is realized.
In one embodiment, when the current of the inductor L1 flows from the positive half cycle to the negative half cycle, the switching tube S3 is still in a conducting state, so as to replace D1 to be conducted, reduce the conduction loss, when the current of the negative half cycle flowing through the switching tube S3 gradually decreases to a set comparison value, turn off the switching tube S3, and ensure that the current flows into the input power grid through the rectifier bridge DB1 when the current of the positive half cycle is conducted.
In one embodiment, when the switching tube S3 is a Mosfet, the magnitude of the voltage vds_s3 across the switching tube S3 can be detected to determine the on current of the switching tube S3, and when the magnitude increases from a lower negative value to a preset value Vth, a rising edge is detected to trigger the switching tube S3 to be turned off.
In order to facilitate understanding of the above technical solutions of the present invention, the following describes in detail the working principle or operation manner of the present invention in the actual process.
In the case of a practical application, the device is,
When the switching tube S1 is conducted and the switching tube S2 is turned off and the switching tube S3 or the diode D1 is conducted, current passes through the switching tube S1, the inductor L1, the transformer T1, the resonant capacitor C2, the switching tube S3 or the diode D1 and the capacitor C1;
When the switching tube S1 turns off the switching tube S2 to be conducted and the switching tube S3 or the diode D1 is conducted, current passes through the switching tube S2, the inductor L1, the transformer T1, the resonance capacitor C2, the switching tube S3 or the diode D1;
when the switching tube S1 is turned on and the switching tube S2 is turned off and the switching tube S3 and the diode D1 are turned off, current is input into the power grid Vin through the switching tube S1, the inductor L1, the transformer T1, the resonant capacitor C2 and the rectifier bridge DB 1;
When the switching tube S1 is turned off and the switching tube S2 is turned on, and the switching tube S3 and the diode D1 are turned off, current is input into the power grid Vin through the switching tube S1, the inductor L1, the transformer T1, the resonant capacitor C2 and the rectifier bridge DB 1.
In summary, the invention provides a single-stage power factor correction control circuit, which can realize power factor correction in a wider input power grid voltage range, reduce current harmonic distortion, limit and stabilize bus capacitor voltage and avoid overstress of devices. According to the single-stage power factor correction control circuit, the voltage of the capacitor C1 is limited and stabilized by controlling the on time of the switch S3, so that overstress of a circuit device is prevented. Meanwhile, the input grid current is sampled, and the capacitance peak voltage represents the current average value through capacitance integration. By adopting a peak control mode and controlling the conduction time of the switch S3, the input current tracks the input grid voltage, and the power factor correction function is realized. The single-stage power factor correction circuit is simple in circuit and convenient to control. The circuit cost is lower compared to a two-stage circuit. Compared with a passive charge pump PFC, the bus capacity voltage and the power factor can be well considered, and the power pump PFC can be suitable for a wider input and output load range.
The foregoing description of the preferred embodiments of the invention is not intended to be limiting, but rather is intended to cover all modifications, equivalents, alternatives, and improvements that fall within the spirit and scope of the invention.
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| CN110808681A (en) * | 2019-11-13 | 2020-02-18 | 杭州优特电源有限公司 | Passive PFC resonant converter and control method thereof |
| CN214014106U (en) * | 2020-11-02 | 2021-08-20 | 安徽乐图电子科技有限公司 | Low-cost single-stage power factor correction control circuit and switching power supply |
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| CN104917412A (en) * | 2015-07-17 | 2015-09-16 | 东南大学 | Single stage power factor correction phase-shift full bridge topology circuit |
| KR102059635B1 (en) * | 2017-12-15 | 2020-02-11 | 부경대학교 산학협력단 | Led power supply and control method thereof |
| CN111629496B (en) * | 2020-06-12 | 2022-01-25 | 英飞特电子（杭州）股份有限公司 | Charge pump control circuit and driving power supply |
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| CN214014106U (en) * | 2020-11-02 | 2021-08-20 | 安徽乐图电子科技有限公司 | Low-cost single-stage power factor correction control circuit and switching power supply |
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