CN112635994A - Microstrip series feed antenna and millimeter wave radar - Google Patents
Microstrip series feed antenna and millimeter wave radar Download PDFInfo
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
- H01Q1/521—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas
- H01Q1/525—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas between emitting and receiving antennas
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
- H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
- H01Q13/10—Resonant slot antennas
- H01Q13/106—Microstrip slot antennas
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q23/00—Antennas with active circuits or circuit elements integrated within them or attached to them
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Abstract
本公开提供了一种微带串馈天线及毫米波雷达，包括介质基板，所述介质基板上设置有若干接收通道和发射通道，所述接收通道、发射通道均和毫米波雷达芯片连接；所述接收通道所在区域和所述发射通道的所在区域相互隔离；所述接收通道和发射通道结构相同，均包括多个微带贴片，所述微带贴片之间通过微带传输线两两相连，且每个微带贴片上设置有两道对称设置的槽。本公开具有易集成、高增益、高角度分辨率、易加工，可实现中、远距离探测的优点。
The present disclosure provides a microstrip string-fed antenna and a millimeter-wave radar, including a dielectric substrate on which a plurality of receiving channels and transmitting channels are arranged, and the receiving channels and transmitting channels are all connected to a millimeter-wave radar chip; The area where the receiving channel is located and the area where the transmitting channel is located are isolated from each other; the receiving channel and the transmitting channel have the same structure, and both include a plurality of microstrip patches, and the microstrip patches are connected two by two through a microstrip transmission line , and each microstrip patch is provided with two symmetrically arranged grooves. The present disclosure has the advantages of easy integration, high gain, high angular resolution, easy processing, and can realize medium and long-distance detection.
Description
Technical Field
The utility model belongs to the technical field of the antenna, concretely relates to microstrip series feed antenna and millimeter wave radar.
Background
The statements in this section merely provide background information related to the present disclosure and may not necessarily constitute prior art.
At present, the millimeter wave radar is widely applied to the fields of medical detection, personnel monitoring, traffic detection and the like, and has the advantages of high detection precision, excellent angle resolution, long detection distance and the like, which are gradually paid attention in recent years. The antenna is an indispensable part of radar as a component for converting electric signals and electromagnetic signals, and among various antenna forms, a microstrip antenna has become a development trend of the frequency band radar antenna due to the advantages of easy integration, low profile, small size, high gain, narrow beam and the like.
However, according to the knowledge of the inventor, due to the technical development limitation and the lack of process precision of processing links such as etching, multi-layer board lamination and the like, the existing microstrip type millimeter wave radar has the following problems:
1. the characteristics of high gain, narrow beam and the like are excessively pursued, so that the integral gain flatness of the radar is poor, the application scene of the product is too narrow, and the product basically has no transportability;
2. the antenna feed part is too complex and the size of the whole machine is seriously influenced due to the adoption of a multi-layer structure and a multi-electronic device (such as a switch diode, a patch capacitor/resistor and the like);
3. the antenna adopting the leaky-wave form has even external field intensity, but sacrifices larger power, and the utilization rate of electromagnetic energy is not high;
4. the slot antenna in the form of a Substrate Integrated Waveguide (SIW) is adopted, the slot antenna combines the advantages of a waveguide and a microstrip and theoretically has better transmission and radiation characteristics, but due to the existence of more slots and grounding through holes, the performance of a design stage is good when the complexity of a millimeter wave frequency band and a gap between the levels of the existing processing technology are considered, but the performance of an actual finished product cannot reach the original design purpose.
Disclosure of Invention
The present disclosure provides a microstrip series-fed antenna and a millimeter wave radar, which have the advantages of easy integration, high gain, high angular resolution, easy processing, and capability of realizing medium and long distance detection.
According to some embodiments, the following technical scheme is adopted in the disclosure:
a microstrip series-fed antenna comprises a dielectric substrate, wherein a plurality of receiving channels and transmitting channels are arranged on the dielectric substrate, and the receiving channels and the transmitting channels are connected with a millimeter wave radar chip;
the area where the receiving channel is located and the area where the transmitting channel is located are mutually isolated;
the receiving channel and the transmitting channel are identical in structure and respectively comprise a plurality of microstrip patches, the microstrip patches are connected with each other in pairs through microstrip transmission lines, and each microstrip patch is provided with two symmetrically-arranged grooves.
In the technical scheme, the transmitting area and the receiving area are divided into two independent areas by an electromagnetic stop band technology, so that the isolation is increased, and mutual interference is reduced; meanwhile, the micro-strip patch is provided with a gap, so that the current distribution of different patches can be controlled, and the level of the side lobe is obviously reduced.
As an alternative embodiment, the microstrip patches are all subjected to a dalf-chebyshev current integration process.
In an alternative embodiment, the width of each microstrip patch in the same channel is the largest at the center, the width of each microstrip patch at the edge is the smallest, and the widths of the microstrip patches at different positions are decreased progressively.
As an alternative implementation, the receiving channel has four channels, the transmitting channel has two channels, and both the receiving channel and the transmitting channel are electrically connected with the millimeter wave radar chip through the coplanar waveguide transmission line.
In an alternative embodiment, the feeding ends of the receiving channel and the transmitting channel are connected to the grounded coplanar waveguide transmission line through a pair of open stubs.
As a further embodiment, the lengths of the pair of open stubs are different.
When the antenna is a 77GHz millimeter wave radar-based antenna, the length of the longer open stub is 1.3mm, and the length of the shorter open stub is 0.2 mm.
In an alternative embodiment, the dielectric substrate has a double-layer structure, and the coplanar waveguide on the upper layer is conducted to the ground on the lower layer through a ground via.
In an alternative embodiment, when the antenna is based on a 77GHz millimeter wave radar, the width of the slot is 0.09 mm.
In an alternative embodiment, the slot is L-shaped, and a short side of the L-shaped slot is located on a side away from the open stub and is disposed inward, and a long side of the L-shaped slot is disposed parallel to a long side of the microstrip patch.
As an alternative embodiment, a grounded electromagnetic resistance band is arranged between the area where the receiving channel is located and the area where the transmitting channel is located, and the width range of the grounded electromagnetic resistance band is ten times or more of the medium wavelength.
As an alternative embodiment, the distance between the area where the receiving channel is located and the area where the transmitting channel is located is greater than a first set value, and the distance between the transmitting channels is greater than a second set value. Both the first and second settings are substantially larger than the medium wavelength.
A millimeter wave radar comprises the microstrip series feed antenna.
And the antenna, the signal layer and the power layer are subjected to press-fit integration processing.
Compared with the prior art, the beneficial effect of this disclosure is:
the method determines the width of the patches and the values of the spacing between the patches by using a Doherty-Chebyshev current synthesis method, and reasonably controls the current distribution of different patches, thereby obviously reducing the level of the side lobe, improving the ratio of the main level to the auxiliary level within a certain range, obviously reducing the mutual interference between antennas, improving the signal-to-noise ratio of a channel and expanding the working range of the radar.
The present disclosure utilizes the patch meander technology to slot the patch, set up through the slot/gap, and the appropriate gap width to achieve the maximized impedance bandwidth, improving the radar angular resolution.
The ground electromagnetic resistance band or the isolation distance is arranged in the transmitting area and the receiving area, so that the mutual interference phenomenon between the transmitting end and the receiving end is effectively reduced, the isolation between the transmitting antennas and the receiving antennas is increased, and the higher transmitting-receiving isolation degree under the same beam width or the wider beam coverage range under the same isolation degree is basically realized.
The antenna provided by the disclosure is integrally modularized, the antenna part of the existing product can be replaced at any time, the antenna has a wide application range, future radar application is facilitated, simple combination can be carried out, a new antenna can be formed, and the development period is greatly shortened.
In order to make the aforementioned objects, features and advantages of the present disclosure more comprehensible, preferred embodiments accompanied with figures are described in detail below.
Drawings
The accompanying drawings, which are included to provide a further understanding of the disclosure, illustrate embodiments of the disclosure and together with the description serve to explain the disclosure and are not to limit the disclosure.
Fig. 1 is a schematic diagram of an antenna structure according to the first embodiment;
fig. 2 is an enlarged schematic view of the antenna structure of the first embodiment;
FIG. 3 is a graph of simulation results of return loss of the antenna according to the second embodiment;
FIG. 4 is a graph of simulation results of the antenna frequency-gain curve of the second embodiment;
fig. 5 is a diagram of simulation results of the level (normalization) of the main and side lobes of the pitch angle of the antenna in the second embodiment;
FIG. 6 is a diagram showing simulation results of the antenna transmit-receive isolation in the second embodiment;
the specific implementation mode is as follows:
the present disclosure is further described with reference to the following drawings and examples.
It should be noted that the following detailed description is exemplary and is intended to provide further explanation of the disclosure. Unless defined otherwise, all technical and scientific terms used herein have the same meaning as commonly understood by one of ordinary skill in the art to which this disclosure belongs.
It is noted that the terminology used herein is for the purpose of describing particular embodiments only and is not intended to be limiting of example embodiments according to the present disclosure. As used herein, the singular forms "a", "an" and "the" are intended to include the plural forms as well, and it should be understood that when the terms "comprises" and/or "comprising" are used in this specification, they specify the presence of stated features, steps, operations, devices, components, and/or combinations thereof, unless the context clearly indicates otherwise.
In the present disclosure, terms such as "upper", "lower", "left", "right", "front", "rear", "vertical", "horizontal", "side", "bottom", and the like indicate orientations or positional relationships based on those shown in the drawings, and are only relational terms determined for convenience in describing structural relationships of the parts or elements of the present disclosure, and do not refer to any parts or elements of the present disclosure, and are not to be construed as limiting the present disclosure.
In the present disclosure, terms such as "fixedly connected", "connected", and the like are to be understood in a broad sense, and mean either a fixed connection or an integrally connected or detachable connection; may be directly connected or indirectly connected through an intermediate. The specific meanings of the above terms in the present disclosure can be determined on a case-by-case basis by persons skilled in the relevant art or technicians, and are not to be construed as limitations of the present disclosure.
The first embodiment is as follows:
as shown in fig. 1, a 77GHz millimeter wave radar antenna is provided.
A millimeter wave radar antenna is realized based on a certain type of 77GHz millimeter wave radar chip, the type of the chip is not limited, and the existing chip can be used. The antenna has the advantages of easy integration (in the embodiment, the antenna can be packaged with a chip through a PBGA technology), high gain, high angular resolution, easy processing and capability of realizing medium-distance and long-distance detection.
As shown in fig. 1, a millimeter wave radar antenna adopts a dual-transmission and four-reception mode, a certain 77GHz millimeter wave radar chip (11) is adopted, 4 receiving channels and 2 transmitting channels are provided in total, 6 radio frequency channels (or called transmitting and receiving antennas) (namely, the receiving channels and the transmitting channels) are welded with a coplanar waveguide transmission line (1) by a packaging technology, and finally, the millimeter wave radar antenna is electrically conducted with 6 terminal transmitting and receiving antennas.
Based on the reciprocity theorem, the 6 transmitting and receiving antennas are completely the same in physical structure and size, and are all 6 microstrip patches (3) which are processed by current tapering, the central positions of the microstrip patches (3) are connected pairwise by microstrip transmission lines (5) which are approximate to half of the medium wavelength, and each microstrip patch (3) is provided with two symmetrical L-shaped gaps (4).
The feed end of the patch antenna is connected to the above-mentioned grounded coplanar waveguide transmission line through a pair of (one short and one long) open stubs (2).
The antenna adopts a double-layer structure, in the embodiment, the dielectric substrate adopts Rogers _ RO4350B (7), the upper coplanar waveguide (6) is conducted with the lower Ground (GND) through a ground through hole (8), and a long and narrow electromagnetic stop band (10) is arranged between the transmitting area and the receiving area.
Of course, in specific application, the antenna layer is generally pressed and integrated with the lower signal layer, the power layer and the like, and is reinforced mechanically by the metal screws (9).
In summary, the first embodiment has good transmit-receive isolation through proper space isolation and design of the grounding electromagnetic resistance band; meanwhile, the purposes of widening impedance bandwidth, double resonance, inhibiting secondary lobe level, high front-to-back ratio, directional diagram control and flat gain curve are achieved through ingenious design including technologies of double-open-circuit branches, Chebyshev current synthesis, patch meander and the like.
Example two:
the difference between the present embodiment and the first embodiment is that the present embodiment further describes the technical solution of the present disclosure in detail by combining specific parameters.
In addition, in this embodiment, in order to increase the isolation between the transmitting antennas and between the transmitting and receiving antennas, the following measures are taken:
a grounding electromagnetic resistance band with proper width (about ten times of medium wavelength) is arranged between the transmitting area and the receiving area, so that the mutual interference phenomenon between the transmitting end and the receiving end is effectively reduced;
or/and:
by adopting the spatial isolation, a proper distance (far greater than the medium wavelength) is selected between the transmitting area and the receiving area, in the embodiment, the distance Gap1 is 7.62mm, and a proper distance (far greater than the medium wavelength) is also selected between the 2 transmitting antennas, in the embodiment, the distance Gap2 is 6.3mm, and the measures effectively increase the isolation between the transmitting antennas and the receiving antennas.
As shown in FIG. 2, in this example, a single-layer Rogers _ RO4350B high-frequency board was used as the dielectric substrate, the board thickness was 0.101mm, the dielectric constant and the loss tangent were 3.66 and 0.004, respectively, at the operating frequency, and the thickness of the upper and lower copper-clad layers was 1 oZ.
The microstrip antenna adopts a dual-transmission four-reception mode, as shown in fig. 2, patches of the microstrip antenna are subjected to dalf-chebyshev current comprehensive processing for current tapering to reduce the side lobe level, the current ratio distributed from the center patch to the patches on both sides is I3: I2: I1 is 1:0.756:0.468, and then the actual width of each patch (decreasing from the center patch to both sides) and the length and width of the transmission line between the patches are respectively W3-1.3 mm, W2-0.98 mm, W1-0.61 mm, L2-0.85 mm, and W4-0.1 mm are optimized by simulation software (in this embodiment, Ansys HFSS, the same below). Further, the patch length L1 is 0.98mm as calculated by the formula for the rectangular linearly polarized patch antenna.
In order to maximize the impedance bandwidth and improve the radar angular resolution, double L-shaped symmetrical slots are innovatively introduced into a patch, a double-open-circuit stub structure is introduced into a feed end, and the optimal impedance bandwidth is obtained when the slot width and the lengths of two open-circuit stubs are respectively W _ slot 0.09mm, L3 0.2mm and L4 1.3mm according to the Schmidth chart impedance calculation and simulation software result optimization. One end of the open stub is connected to a microstrip transmission line to form electrical continuity, and the transmission line has an appropriate width W _ feed of 0.18mm as calculated by an impedance calculator.
Of course, in other embodiments, any one or more of the above parameters may be varied.
In the embodiment, the electromagnetic resistance band technology is used for dividing the transmitting area and the receiving area into two independent areas, so that the isolation is increased, and the mutual interference is reduced.
Meanwhile, experimental simulation shows that the following effects are achieved:
1. impedance bandwidth (on 10dB basis) boost:
as shown in FIG. 3, the 10dB bandwidth of the present embodiment covers 76G-81GHz, the relative bandwidth is above 6%, and the impedance bandwidth is improved by more than 30% compared with the similar products in the market (the 10dB bandwidth of the similar products is usually within 3 GHz).
2. Gain flatness improvement:
because the series-fed antenna has the characteristic of a frequency-sweeping antenna (namely, the direction of a main lobe of a wave beam changes along with the change of input frequency), the continuous change of the maximum gain direction often occurs when the radar works, and the application of the radar in a scene under a fixed angle is not facilitated; as shown in FIG. 4, the gain variation in the normal direction of the present embodiment is within 2.5dB in 76-81GHz, which is reduced by 30-50% compared with similar products in the market.
3. Lower side lobe level:
the embodiment adopts the Chebyshev current synthesis method, reasonably controls the current distribution of different patches through tapering the patch current, thereby obviously reducing the side lobe level, and the ratio of the main level to the auxiliary level is more than 16dB, thereby obviously reducing the mutual interference between the antennas and improving the signal-to-noise ratio of a channel.
4. Transmitting terminal and receiving terminal
As shown in fig. 6, through simulation experiments, the transmit-receive isolation (between two nearest receiving and transmitting antennas) in the 76-81GHz operating band of this embodiment is above 30dB, which reaches the high level of similar products in the market, and basically realizes a higher transmit-receive isolation under the same beam width or a wider beam coverage under the same isolation.
Example three:
a radar to which the antenna of the above embodiment is applied.
The above description is only a preferred embodiment of the present disclosure and is not intended to limit the present disclosure, and various modifications and changes may be made to the present disclosure by those skilled in the art. Any modification, equivalent replacement, improvement and the like made within the spirit and principle of the present disclosure should be included in the protection scope of the present disclosure.
Although the present disclosure has been described with reference to specific embodiments, it should be understood that the scope of the present disclosure is not limited thereto, and those skilled in the art will appreciate that various modifications and changes can be made without departing from the spirit and scope of the present disclosure.
Claims (12)
1. A microstrip series-feed antenna is characterized in that: the millimeter wave radar antenna comprises a dielectric substrate, wherein a plurality of receiving channels and transmitting channels are arranged on the dielectric substrate, and the receiving channels and the transmitting channels are connected with a millimeter wave radar chip;
the area where the receiving channel is located and the area where the transmitting channel is located are mutually isolated;
the receiving channel and the transmitting channel are identical in structure and respectively comprise a plurality of microstrip patches, the microstrip patches are connected with each other in pairs through microstrip transmission lines, and each microstrip patch is provided with two symmetrically-arranged grooves.
2. The microstrip series feed antenna as claimed in claim 1, wherein: the microstrip patches are subjected to dalf-chebyshev current comprehensive treatment.
3. The microstrip series feed antenna as claimed in claim 1, wherein: the width of each microstrip patch in the same channel is the largest at the center, the width of each microstrip patch at the edge is the smallest, and the widths of the microstrip patches at different positions are decreased progressively.
4. The microstrip series feed antenna as claimed in claim 1, wherein: the receiving channel has four paths, the transmitting channel has two paths, and the receiving channel and the transmitting channel are electrically connected with the millimeter wave radar chip through the coplanar waveguide transmission line.
5. The microstrip series feed antenna as claimed in claim 4, wherein: and the feed ends of the receiving channel and the transmitting channel are connected with the grounded coplanar waveguide transmission line through a pair of open circuit stubs.
6. The microstrip series feed antenna as claimed in claim 4, wherein: the lengths of the pair of open circuit stubs are different;
or further, when the antenna is based on a 77GHz millimeter wave radar, the length of the longer open-circuit stub is 1.3mm, and the length of the shorter open-circuit stub is 0.2 mm.
7. The microstrip series feed antenna as claimed in claim 1, wherein: the medium substrate is of a double-layer structure, and the coplanar waveguide on the upper layer is conducted with the ground on the lower layer through the grounding through hole.
8. The microstrip series feed antenna as claimed in claim 1, wherein: when the antenna is based on a 77GHz millimeter wave radar, the width of the slot is 0.09 mm.
9. The microstrip series feed antenna as claimed in claim 1, wherein: the groove is L-shaped, the short edge of the L-shaped groove is located on one side far away from the open stub and is arranged towards the inner side, and the long edge of the L-shaped groove is parallel to the long edge of the microstrip patch.
10. The microstrip series feed antenna as claimed in claim 1, wherein: and a grounding electromagnetic resistance band is arranged between the area where the receiving channel is located and the area where the transmitting channel is located, and the width range of the grounding electromagnetic resistance band is eight times of medium wavelength to twelve times of medium wavelength.
11. The microstrip series feed antenna as claimed in claim 1, wherein: the distance between the area where the receiving channel is located and the area where the transmitting channel is located is larger than a first set value, and the distance between the transmitting channels is larger than a second set value.
12. A millimeter wave radar is characterized in that: comprising a microstrip series fed antenna according to any of claims 1-11.
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Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN113659326A (en) * | 2021-08-18 | 2021-11-16 | 英特睿达(山东)电子科技有限公司 | Millimeter wave microstrip antenna and millimeter wave radar based on electromagnetic band gap structure |
| CN114843770A (en) * | 2022-04-19 | 2022-08-02 | 福思(杭州)智能科技有限公司 | Microstrip antenna and millimeter wave radar |
| CN116031663A (en) * | 2023-02-10 | 2023-04-28 | 西安电子科技大学 | A microstrip string-fed line array antenna with beam deflection suppression function |
| CN117111050A (en) * | 2023-08-31 | 2023-11-24 | 中咨泰克交通工程集团有限公司 | Long-distance roadside millimeter wave radar detection system |
| CN117791129A (en) * | 2023-12-28 | 2024-03-29 | 南京林业大学 | A design method for automotive phased array antenna based on large-angle scanning range |
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| CN113659326A (en) * | 2021-08-18 | 2021-11-16 | 英特睿达(山东)电子科技有限公司 | Millimeter wave microstrip antenna and millimeter wave radar based on electromagnetic band gap structure |
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| CN114843770A (en) * | 2022-04-19 | 2022-08-02 | 福思(杭州)智能科技有限公司 | Microstrip antenna and millimeter wave radar |
| CN116031663A (en) * | 2023-02-10 | 2023-04-28 | 西安电子科技大学 | A microstrip string-fed line array antenna with beam deflection suppression function |
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