CN120113143A - Air conditioning control system and harmonic suppression method thereof - Google Patents

Abstract

Some embodiments of the present disclosure provide an air conditioner control system and a harmonic control method thereof, the air conditioner control system including an inverse pek converter, a motor, and a compensator. The inverse park converter is configured to output a first voltage and a second voltage. The motor includes a first shaft and a second shaft. The first voltage is input to the first shaft and the second voltage is input to the second shaft. The compensator is configured to determine a target damping coefficient and a first damping power, the target damping coefficient being derived based on an equivalent power of the motor and a direct current component of a busbar voltage thereof, the first damping power being configured as a power characterizing a fluctuating component of the busbar voltage, the second damping power being determined based on the target damping coefficient and the first damping power, the first voltage compensation component of the first shaft and the second voltage compensation component of the second shaft being determined based on the second damping power, the first current of the first shaft and the second current of the second shaft, and the first voltage compensation component being superimposed to the first voltage and the second voltage compensation component being superimposed to the second voltage, respectively.

Description

Air conditioner control system and harmonic suppression method thereof

The present application claims priority from chinese patent application No. 202310088599.8 filed on month 02, 2023 and 01, and priority from chinese patent application No. 202310090099.8 filed on month 02, 2023, which are incorporated herein by reference in their entirety.

Technical Field

The present disclosure relates to the field of air conditioning technologies, and in particular, to an air conditioner control system and a harmonic suppression method thereof.

Background

Permanent magnet synchronous motors are widely applied to the scenes of aerospace, industrial transmission, household appliances and the like as electromechanical transduction devices. The capacitor in the permanent magnet synchronous motor driving system can use an electrolytic capacitor or a non-electrolytic capacitor, and the permanent magnet synchronous motor driving system using the electrolytic capacitor has the advantages of huge volume, high cost and low service life, so that the traditional electrolytic capacitor is replaced by a thin film capacitor or a ceramic capacitor.

Disclosure of Invention

In one aspect, an air conditioning control system is provided that includes an inverse pek inverter, a motor, and a compensator. The inverse Peak converter is configured to output a first voltage and a second voltage. The motor is coupled with the inverse pek transformer, the motor including a first shaft and a second shaft. The first voltage is input to the first shaft and the second voltage is input to the second shaft. The compensator is configured to determine a target damping coefficient based on an equivalent power of the motor and a direct current component of a bus voltage thereof, and a first damping power configured to characterize a power of a fluctuating component of the bus voltage, determine a second damping power based on the target damping coefficient and the first damping power, determine a first voltage compensation component of the first shaft and a second voltage compensation component of the second shaft based on the second damping power, a first current of the first shaft, and a second current of the second shaft, respectively, and superimpose the first voltage compensation component on the first voltage and the second voltage compensation component on the second voltage, respectively, to better suppress harmonics.

In another aspect, an air conditioner control system is provided that includes a comparator device, a proportional amplifying operation device, a phase operation device, a damping voltage generation device, a first addition operation device, a second addition operation device, and a controller. The comparator means is configured to compare the same-frequency sawtooth wave with a given value of the sawtooth wave to obtain a rectangular wave. The proportional amplifying operation device is coupled with the comparator device and is configured to amplify the rectangular wave to obtain a given damping pulse. The phase operation device is coupled with the proportional amplification operation device and is configured to perform phase shift on the given damping pulse according to the three-phase current on the network side to obtain an applied damping pulse. The damping voltage generating device is coupled to the phase computing device and is configured to obtain a first voltage compensation component and a second voltage compensation component according to the applied damping pulse. The first addition operation device is coupled with the damping voltage generation device and is configured to superimpose the first voltage compensation component on a first voltage to obtain a first voltage command, and output the first voltage command to the space vector pulse width modulation operation device. The second addition operation device is coupled with the damping voltage generation device and is configured to superimpose the second voltage compensation component on a second voltage to obtain a second voltage instruction, and the second voltage instruction is output to the space vector pulse width modulation operation device. The controller is coupled with the comparator device, the proportional amplifying operation device, the phase operation device, the damping voltage generation device, the first addition operation device and the second addition operation device, and is configured to acquire the same-frequency sawtooth wave, and the same-frequency sawtooth wave is generated according to LC resonance frequency.

In yet another aspect, a method of harmonic rejection of an air conditioning control system is provided, wherein the air conditioning control system includes an inverse pek inverter, a motor, and a compensator. The inverse Peak converter is configured to output a first voltage and a second voltage. The motor is coupled with the inverse pek transformer and the compensator, respectively, and includes a first shaft and a second shaft. The first voltage is input to the first shaft and the second voltage is input to the second shaft. The compensator is coupled with the inverse Pake converter and the motor. The harmonic suppression method includes determining a target damping coefficient and a first damping power, the target damping coefficient being derived based on an equivalent power of a motor and a direct current component of a bus voltage, the first damping power being configured to be a power characterizing a fluctuating component of the bus voltage, determining a second damping power based on the target damping coefficient and the first damping power, determining a first voltage compensation component of the first shaft and a second voltage compensation component of the second shaft based on the second damping power, a first current of the first shaft, and a second current of the second shaft, respectively, and superimposing the first voltage compensation component to the first voltage and the second voltage compensation component to the second voltage.

In still another aspect, an air conditioner control system harmonic suppression method is provided, wherein the air conditioner control system includes a comparator device, a proportional amplifying operation device, a phase operation device, a damping voltage generation device, a first addition operation device, a second addition operation device, and a controller. The proportional amplifying operation device is coupled with the comparator device. The phase operation device is coupled with the proportional amplification operation device. The damping voltage generating device is coupled with the phase operation device. The first adding device is coupled with the damping voltage generating device. The second adding device is coupled with the damping voltage generating device. The controller is coupled to the comparator device, the proportional amplifying operation device, the phase operation device, the damping voltage generating device, the first addition operation device and the second addition operation device. The harmonic suppression method comprises the steps of obtaining common-frequency sawtooth waves, generating the common-frequency sawtooth waves according to LC resonance frequency, comparing the common-frequency sawtooth waves with given values of the sawtooth waves to obtain rectangular waves, amplifying the rectangular waves to obtain given damping pulses, performing phase shifting on the given damping pulses according to net-side three-phase currents to obtain applied damping pulses, obtaining first voltage compensation components and second voltage compensation components according to the applied damping pulses, superposing the first voltage compensation components on the first voltage to obtain a first voltage command, superposing the second voltage compensation components on the second voltage to obtain a second voltage command, and applying the first voltage command and the second voltage command to a space vector pulse width modulation operation device.

Drawings

Fig.1 is a block diagram of an air conditioning control system according to some embodiments;

FIG.2 is a flow chart of a method of harmonic suppression according to some embodiments;

FIG.3 is a flow chart of another harmonic suppression method according to some embodiments;

FIG.4 is a flow chart of yet another harmonic suppression method according to some embodiments;

FIG.5 is a block diagram of another air conditioning control system according to some embodiments;

FIG. 6 is a graph of current and voltage ripple spectra without superimposed compensation components according to some embodiments;

FIG. 7 is a graph of current and voltage ripple spectra after superimposing compensation components according to some embodiments;

FIG. 8 is a block diagram of a compensator according to some embodiments;

Fig.9 is a block diagram of yet another air conditioning control system according to some embodiments;

FIG. 10 is a diagram of a damping voltage generation unit according to some embodiments;

FIG. 11 is a flow chart of yet another harmonic suppression method according to some embodiments;

FIG. 12 is a common frequency sawtooth waveform diagram according to some embodiments;

FIG. 13 is a waveform diagram of common frequency sawtooth set point waveforms, according to some embodiments;

FIG. 14 is a rectangular wave waveform diagram according to some embodiments;

FIG. 15 is a flow chart of yet another harmonic suppression method according to some embodiments;

FIG.16 is a flow chart of yet another harmonic suppression method according to some embodiments;

FIG.17 is a flow chart of yet another harmonic suppression method according to some embodiments;

FIG. 18 is a block diagram of a controller according to some embodiments;

Fig. 19 is a block diagram of a controller according to some embodiments.

Detailed Description

Some embodiments of the present disclosure will now be described more fully hereinafter with reference to the accompanying drawings, in which it is evident that the embodiments described are only some, but not all embodiments of the disclosure. All other embodiments obtained by one of ordinary skill in the art based on the embodiments provided by the present disclosure are within the scope of the present disclosure.

Throughout the specification and claims, unless the context requires otherwise, the word "comprise" and its other forms such as the third person referring to the singular form "comprise" and the present word "comprising" are to be construed as open, inclusive meaning, i.e. as "comprising, but not limited to. In the description of the specification, the terms "one embodiment", "some embodiments (some embodiments)", "exemplary embodiment (exemplary embodiments)", "example (example)", "specific example (some examples)", etc. are intended to indicate that a particular feature, structure, material, or characteristic associated with the embodiment or example is included in at least one embodiment or example of the present disclosure. The schematic representations of the above terms do not necessarily refer to the same embodiment or example. Furthermore, the particular features, structures, materials, or characteristics may be combined in any suitable manner in any one or more embodiments or examples.

The terms "first" and "second" are used below for descriptive purposes only and are not to be construed as indicating or implying relative importance or implicitly indicating the number of technical features indicated. Thus, a feature defining "a first" or "a second" may explicitly or implicitly include one or more such feature. In the description of the embodiments of the present disclosure, unless otherwise indicated, the meaning of "a plurality" is two or more.

In describing some embodiments, expressions of "coupled" and "connected" and their derivatives may be used. The term "coupled" is used in a broad sense, and may be either permanently coupled, detachably coupled, or integrally formed, or indirectly coupled via an intervening medium, for example. The term "coupled" for example, indicates that two or more elements are in direct physical or electrical contact. The term "coupled" or "communicatively coupled (communicatively coupled)" may also mean that two or more elements are not in direct contact with each other, but yet still co-operate or interact with each other. The embodiments disclosed herein are not necessarily limited to the disclosure herein.

"A and/or B" includes three combinations of A only, B only, and a combination of A and B.

The use of "adapted" or "configured to" herein is meant to be an open and inclusive language that does not exclude devices adapted or configured to perform additional tasks or steps.

In addition, the use of "based on" is intended to be open and inclusive in that a process, step, calculation, or other action "based on" one or more of the stated conditions or values may be based on additional conditions or beyond the stated values in practice.

First, proper nouns to which the present disclosure relates are described.

The higher harmonic (high order harmonic) is expressed by the Fourier series decomposition of any composite periodic vibration function Y (T), wherein the first term is the mean value or the direct current component, the second term is the fundamental wave or the basic vibration, the third term is the second harmonic, and the second harmonic is hereinafter collectively called higher harmonic. The sine waves having a frequency greater than or equal to 2 times the frequency of the fundamental wave are both higher harmonics.

Negative resistance, also known as negative differential resistance, is a characteristic of a voltage decrease when the current at a particular port of a circuit or electronic component increases, as opposed to resistance.

The Low-pass filtering (Low-PASS FILTER), also called High-cut Filter or highest cut Filter, is a filtering mode, and the filtering rule is that the Low-frequency signal can normally pass through, the High-frequency signal exceeding the set frequency is blocked and weakened in the filtering process, and the blocking and weakening amplitude of the High-frequency signal can be changed according to different frequencies and different filtering programs (purposes).

The Band pass filter (Band-PASS FILTER) is a device that allows waves of a specific frequency Band to pass while shielding other frequency bands. For example, a Resistor-inductor-capacitor oscillator-capacitor (RLC) is an analog bandpass filter. Band-pass filtering refers to a filtering method for filtering out high-frequency signals and low-frequency signals and reserving intermediate-frequency signals.

The direct current component of a signal refers to the average value of the signal, which is a constant independent of time. If the original signal is a periodic signal, the process of taking the limit may be omitted when expressed by a mathematical formula, and the integration limit (the lower limit and the upper limit of the integration are defined) may take any one period.

The Park's transformation (Park transformation) is one of the most commonly used coordinate transformations for analyzing synchronous motor operation. The park transformation projects a, b and c three-phase currents of the stator to a direct axis (d axis) rotating along with the rotor, and an intersecting axis (q axis) and a zero axis (0 axis) perpendicular to the dq plane are obtained, namely, the abc coordinate system is transformed to the dq coordinate system, so that diagonalization of a stator inductance matrix is realized, and the operation analysis of the synchronous motor is simplified.

A Permanent Magnet Synchronous Motor (PMSM), which is a type of synchronous motor in which a rotor has permanent magnets instead of windings.

A Proportional and integral regulator (PI regulator) is a linear controller that forms a control deviation from a given value and an actual output value, and forms a control quantity by linearly combining the Proportional and integral of the deviation to control a controlled object.

The Clark transform (Clarke Transformation) converts the forward current in a three-phase stationary 120 degree coordinate system (e.g., a-b-c coordinate system) to a two-phase stationary rectangular coordinate system (e.g., an α - β coordinate system).

In a permanent magnet synchronous motor driving system, the capacitor can be an electrolytic capacitor or an electroless capacitor, and the permanent magnet synchronous motor driving system using the electrolytic capacitor has the advantages of huge volume, high cost and low service life.

In some embodiments, in the power grid, harmonics are generated due to the presence of a non-linear load, i.e. the applied voltage is not linearly (proportional) related to the current flowing through the non-linear load, resulting in a non-sinusoidal current. In order to filter out harmonic waves in a power grid, a reactor is added on the grid side of a permanent magnet synchronous motor driving system, however, in the film capacitor driving system, the capacitance value of the film capacitor is smaller, no electrolytic capacitor is used for storing energy and smoothing the DC pulsating voltage, so that the bus voltage generates periodic fluctuation, the resistance value of an input line is smaller, the damping capacity of the system is weaker, and an LC resonance phenomenon is easy to occur between an inductor and the bus film capacitor. In addition, as the alternating current motor can be equivalent to a constant power load, the thin film capacitor driving system presents negative impedance characteristics, and the characteristics can lead to the amplification of harmonic waves at LC resonance frequency, so that serious harmonic waves appear in network side current, further the network side power quality is poor, and the efficiency of the thin film capacitor driving system is reduced.

In the related art, in order to improve the network-side power quality, in a suppression strategy of bus voltage feedback resonance, a resonance phenomenon is generally suppressed by injecting a compensation voltage with a fixed amplitude. However, when the operating power of the thin film capacitor driving system increases, the effect of suppressing resonance by the compensation voltage of a fixed magnitude decreases, resulting in failure to accurately suppress resonance.

To solve the above-mentioned problems, some embodiments of the present disclosure provide an air conditioner control system 10, where the air conditioner control system 10 is, for example, a thin film capacitor driving system 10, and the air conditioner control system 10 suppresses harmonics in the voltage through the voltage compensation component, so as to improve the network side current quality. The air conditioning control system 10 includes a motor and a compensator, and is capable of determining and adjusting a first voltage compensation component and a second voltage compensation component according to the power of the motor, and adding the first voltage compensation component to the first voltage and adding the second voltage compensation component to the second voltage through the compensator to better suppress harmonics, thereby improving network side power quality.

It should be noted that the thin film capacitor driving system 10 may be applied to various control systems, for example, may be applied to an air conditioning system. The air conditioning system comprises a multi-split air conditioning system.

Fig. 1 is a block diagram of an air conditioning control system according to some embodiments, as shown in fig. 1, in some embodiments of the present disclosure, an air conditioning control system 10 includes a motor 101, a compensator 102, and an inverse pek inverter 103. The motor 101 is coupled to an inverse pi converter 103 and a compensator 102, respectively.

The compensator 102 is configured to determine a target damping coefficient and a first damping power. In some embodiments of the present disclosure, the compensator 102 includes a band pass filter 1021 and a low pass filter 1022, the band pass filter 1021 can band pass filter the bus voltage, the low pass filter 1022 can low pass filter the bus voltage, i.e., the compensator 102 can band pass filter or at least one of low pass filter the bus voltage.

In some embodiments of the present disclosure, compensator 102 may further comprise an acquisition component configured to acquire values of the bus voltage, the first current, the first voltage, the second current, and the second voltage.

In some embodiments of the present disclosure, the compensator 102 may further include a processing component that calculates a first voltage compensation component and a second voltage compensation component according to the bus voltage, the first current, the first voltage, the second current, and the second voltage acquired by the acquisition component.

The inverse park converter 103 is configured to output a first voltage and a second voltage.

In some embodiments of the present disclosure, in the air conditioning control system 10, a first voltage compensation component is superimposed to a first voltage to generate a first voltage command, and a second voltage compensation component is superimposed to a second voltage to generate a second voltage command.

In some embodiments of the present disclosure, the motor 101 may be a permanent magnet synchronous motor, such as a three-phase film capacitor inverter permanent magnet synchronous motor, or a brushless dc motor. The motor 101 operates according to the voltage output from the compensator 102 and the inverse pi-gram converter 103. In some embodiments of the present disclosure, the motor 101 includes a first shaft 1011 (e.g., an alpha axis) and a second shaft 1012 (e.g., a beta axis). The α axis and the β axis are two stationary rectangular coordinate systems established by the motor 101, and the coordinate systems are stationary.

Fig. 2 is a flowchart of a harmonic suppression method according to some embodiments, and in order to improve network-side power quality, some embodiments of the present disclosure provide a harmonic suppression method of an air conditioner control system 10, applied to a compensator 102, as shown in fig. 2, and in some embodiments of the present disclosure, the method includes S201-S204.

S201, determining a target damping coefficient (i.e., an adaptive damping coefficient) and a first damping power.

Wherein the target damping coefficient is derived based on the equivalent power of the motor 101 and the dc component of the bus voltage, in some embodiments of the present disclosure, the compensator 102 obtains the equivalent power of the motor 101 and the dc component of the bus voltage, and determines the quotient of the equivalent power and the square of the dc component as the target damping coefficient.

After the bus voltage is obtained, the compensator 102 extracts a direct current component by low-pass filtering the bus voltage. Furthermore, the compensator 102 also obtains a first voltage and a first current of the first shaft 1011 of the motor 101 and a second voltage and a second current of the second shaft 1012 of the motor 101. In some embodiments of the present disclosure, the equivalent power of the motor 101 is the power of the motor 101 at the current time.

In some embodiments of the present disclosure, compensator 102 substitutes the first current, the first voltage, the second current, and the second voltage into equation one to determine the equivalent power of motor 101. P ₁＝N×(U_α×I_α+U_β×I_β) equation one

Wherein, P ₁ is the equivalent power of the motor 101, N is a preset value, U _α is the first voltage of the first shaft 1011, I _α is the first current of the first shaft 1011, U _β is the second voltage of the second shaft 1012, and I _β is the second current of the second shaft 1012.

In some embodiments of the present disclosure, the preset value N is set according to the condition of the driving circuit in the air conditioning control system 10, for example, n=1.5.

Further, the compensator 102 determines the dc component of the bus voltage, calculates the square value U _d of the dc component, and substitutes the equivalent power P ₁ and the square value U _d of the dc component into the formula two to obtain the target damping coefficient. The second formula is obtained according to the Lawster criterion. P ₁/U_d =y formula two

Wherein P ₁ is the equivalent power of the motor 101, U _d is the square value of the DC component, and Y is the target damping coefficient.

It will be appreciated that since the equivalent power is the power of the motor 101 at the current time, the adaptive damping coefficient may be determined according to the equivalent power of the motor 101 at the current time, so that the air conditioner control system 10 may adaptively adjust the motor 101.

In some embodiments of the present disclosure, the compensator 102 performs low-pass filtering on the bus voltage based on a preset low-pass filtering algorithm to obtain a dc component of the bus voltage. The formula of the preset low-pass filtering algorithm is, for example, formula three.

Wherein U _dc is a direct current component, S is a complex variable in Law transformation, omega _L is a cut-off frequency of a low-pass filter, and U is a bus voltage.

In some embodiments of the present disclosure, ω _L is, for example, 100Hz.

The first damping power is configured to characterize the power of the fluctuating component of the bus voltage.

In some embodiments of the present disclosure, the compensator 102 extracts the ripple component by bandpass filtering the bus voltage after obtaining the bus voltage, and obtains the first damping power according to the ripple component and the bus voltage. For example, the compensator 102 determines the fluctuating component of the bus voltage by a preset bandpass filtering algorithm.

It should be noted that, the preset low-pass filtering algorithm and the preset band-pass filtering algorithm are preset in the compensator 102.

S202, determining second damping power (namely self-adaptive damping power) based on the target damping coefficient and the first damping power.

In some embodiments of the present disclosure, the compensator 102 determines a product of the target damping coefficient Y and the first damping power as the second damping power in the case of acquiring the target damping coefficient Y and the first damping power.

For example, a system transfer function, such as equation four, can be calculated from the bus voltage closed loop system.

Wherein S is a complex variable in the rah transform, L _g is a net side current inductance, C is a bus capacitor, Y is a target damping coefficient, U _d is a square value of a direct current component, R _g is a net side equivalent resistance, and P ₁ is an equivalent power of the motor 101.

Further, substituting the target damping coefficient and the first damping power into the fifth formula to obtain the second damping power. P ₂＝Y×P_d equation five

Wherein P ₂ is the second damping power, Y is the target damping coefficient, and P _d is the first damping power.

In this way, the second damping power at the present moment can be determined from the equivalent power at the present moment of the motor 101.

S203, determining a first voltage compensation component of the first shaft 1011 and a second voltage compensation component of the second shaft 1012 based on the second damping power, the first current of the first shaft 1011, and the second current of the second shaft 1012, respectively.

In some embodiments of the present disclosure, the compensator 102 obtains a first current of the first shaft 1011 and a second current of the second shaft 1012, and determines a first voltage compensation component of the first shaft 1011 and a second voltage compensation component of the second shaft 1012 according to a compensation algorithm based on the second damping power, the first current, the second current, and the preset.

S204, respectively adding the first voltage compensation component to the first voltage and adding the second voltage compensation component to the second voltage.

In some embodiments of the present disclosure, the compensator 102 superimposes the first voltage compensation component on the first voltage of the first axis 1011 and the second voltage compensation component on the second voltage of the second axis 1012 after determining the first voltage compensation component and the second voltage compensation component.

Therefore, harmonic waves can be better suppressed, and therefore network side electric energy quality is improved.

Fig.3 is a flow chart of another harmonic suppression method according to some embodiments, as shown in fig.3, in some embodiments of the present disclosure, S203 includes S2031-S2035 for determining a first voltage compensation component and a second voltage compensation component.

S2031, multiplying the second damping power P ₂ by the first current I _α to obtain a first value P ₂×I_α.

S2032 is to square the first currentSquare value of second currentMultiplying to obtain a second value

S2033, determining a quotient of the first value and the second value as the first voltage compensation component.

For example, the compensator 102 substitutes the first value and the second value into formula six to obtain the first voltage compensation component Δu _α.

Where ΔU _α is the first voltage compensation component, P ₂ is the second damping power, I _α is the first current of the first shaft 1011, and I _β is the second current of the second shaft 1012.

S2034, multiplying the second damping power P ₂ by the second current I _β to obtain a third value P ₂×I_β.

S2035, determining a quotient of the third value and the second value as the second voltage compensation component.

For example, the compensator 102 substitutes the third value and the second value into equation seven to obtain the second voltage compensation component Δu _β.

Where ΔU _β is the second voltage compensation component, P ₂ is the second damping power, I _α is the first current of the first axis, and I _β is the second current of the second axis.

Fig. 4 is a flow chart of yet another harmonic suppression method according to some embodiments, in which, in order to determine the first damping power, S201 includes S2011-S2012 as shown in fig. 4.

S2011, determining a fluctuation component through a preset band-pass filtering algorithm.

The compensator 102 performs band-pass filtering on the busbar voltage based on a preset band-pass filtering algorithm to obtain a busbar voltage fluctuation component.

In some embodiments of the present disclosure, the formula of the preset band-pass filtering algorithm is, for example, formula eight.

Wherein U _C is a fluctuation component, ζ is a damping ratio of the band-pass filter 1021, S is a complex variable in Law transformation, ω is a center angular frequency of the band-pass filter, and U is a bus voltage.

In some embodiments of the present disclosure, ζ is, for example, 0.707, ω is, for example, 300 hertz Hz.

And S2012, determining the product of the fluctuation component and the bus voltage as the first damping power.

For example, the compensator 102 substitutes the ripple component and the bus voltage into formula nine to obtain the first damping power. P _d＝U*U_c formula nine

Wherein P _d is the first damping power, U _C is the fluctuation component, and U is the bus voltage.

Fig. 5 is a block diagram of another air conditioning control system according to some embodiments, and for clarity of illustration of the air conditioning control system 10 provided by embodiments of the present disclosure, as shown in fig. 5, the air conditioning control system 10 includes a compensator 102 and a dual closed loop vector control subsystem 12.

In some embodiments of the present disclosure, the compensator 102 comprises a first damping power device 111, the first damping power device 111 being configured to determine a first damping power P _d from the bus voltage. In some embodiments of the present disclosure, the first damping power device 111 may include a band pass filter G _BPF.

In some embodiments of the present disclosure, the compensator 102 further comprises a target damping coefficient device 112, the target damping coefficient device 112 being configured to determine the target damping coefficient from the bus voltage, the first current, the second current, and the second voltage. In some embodiments of the present disclosure, the target damping coefficient device 112 may include a low pass filter G _LPF, a first calculation component 1121, and a second calculation component 1122. The first calculation component is configured to calculate a square value of the direct current component and the second calculation component 1122 is configured to calculate an equivalent power of the motor 101.

In some embodiments of the present disclosure, the compensator 102 further comprises a second damping power device 113, the second damping power device 113 being configured to determine the second damping power P ₂ in accordance with.

In some embodiments of the present disclosure, the compensator 102 further comprises a voltage compensation component device 114, the voltage compensation component device 114 being configured to determine a first voltage compensation component Δu _α and a second voltage compensation component Δu _β and to superimpose the first voltage compensation component Δu _α on the first voltage and the second voltage compensation component Δu _β on the second voltage, respectively.

The second damping power device 113 is coupled to the first damping power device 111, the target damping coefficient device 112, and the voltage compensation component device 114, respectively. The target damping coefficient device 112 is coupled to the voltage compensation component device 114.

In some embodiments of the present disclosure, dual closed loop vector control subsystem 12 includes a speed regulator 121, speed regulator 121 comprising autoleveling links configured to automatically adjust controlled parameters of the pressure, tension, speed, temperature, etc. parameters comprising the system.

In some embodiments of the present disclosure, dual closed loop vector control subsystem 12 further includes a current regulator 122, current regulator 122 being an electronic device that regulates circuit current to increase reactance.

In some embodiments of the present disclosure, the dual closed loop vector control subsystem 12 further includes an inverse park transformation device 123, the inverse park transformation device 123 configured to command voltages in a two-phase rotating coordinate systemAndTo voltages U _α and U _β in a two-phase stationary coordinate system.

In some embodiments of the present disclosure, the dual closed-loop vector control subsystem 12 further includes a space vector pulse width modulation (Space Vector Pulse Width Modulation, SVPWM) computing device 124, where the space vector pulse width modulation computing device 124 mainly uses the ideal flux linkage circle of the three-phase symmetric motor stator as a reference standard when power is supplied by the three-phase symmetric sine wave voltage, and switches the three-phase inverter in different switching modes, so as to form a PWM wave, i.e., a pulse width modulation waveform, and tracks the accurate flux linkage circle thereof by using the formed actual flux linkage vector. The sine pulse width modulation (Sinusoidal PWM, SPWM) method is from the power source perspective to generate a sine wave power source with adjustable frequency and voltage, while the SVPWM method considers the inverter system and the motor 101 as a whole, and the model is simpler and is also convenient for the control of the microprocessor.

In some embodiments, the three-phase full bridge is typically three half-bridges of six switching devices, and the six switching device combinations (signals of upper and lower half-bridges of the same bridge arm are opposite) have 8 operating states in total. When the switching states of the three upper arms are 000 or 111, no effective current is generated in the motor 101, so that 000 and 111 are called zero vectors. The remaining 6 switch states, except 000 and 111, are six effective vectors, which divide the 360 degree voltage space into six sectors based on 60 degree one sector, and any vector within 360 degrees can be synthesized by six basic effective vectors and two zero vectors, respectively. When a certain vector needs to be synthesized, the vector is decomposed into two basic vectors closest to the vector, and then the two basic vectors are used for representation. It should be noted that the magnitude of the action of each basic vector is characterized by the duration of the action, so that the required voltage vectors can be synthesized according to different time proportions, thereby ensuring that the generated voltage waveform approximates to a sine wave.

When the variable frequency motor is driven, the vector direction is continuously changed, so that the vector acting time needs to be continuously calculated. In synthesizing the vectors, the calculation can be performed by a timer (such as calculating once every 0.1 ms), so that only the time of acting two basic vectors in 0.1ms is needed to be calculated. When the sum of the calculated two times is less than 0.1ms, a proper amount of zero vector is inserted in the rest time. It will be appreciated that in doing the above-described processing of vectors, the resultant drive waveform is similar to PWM and may therefore be referred to as PWM, and that such PWM is based on voltage space vector synthesis and is therefore referred to as SVPWM.

In some embodiments of the present disclosure, dual closed loop vector control subsystem 12 further includes a three-phase thin film capacitive driver 125, three-phase thin film capacitive driver 125 configured to implement variable frequency drive.

In some embodiments of the present disclosure, the dual closed loop vector control subsystem 12 further includes a permanent magnet synchronous motor 126, where the permanent magnet synchronous motor 126 refers to a permanent magnet synchronous motor that distinguishes between defined sinusoidal back emf according to the back emf of the motor 101.

In some embodiments of the present disclosure, the motor 101 includes a direct axis (d-axis) and a quadrature axis (q-axis), where the d-axis and the q-axis are a coordinate system established on the rotor of the motor 101, and the coordinate system rotates synchronously with the rotor, taking the direction of the rotor magnetic field as the d-axis and the direction perpendicular to the rotor magnetic field as the q-axis.

In some embodiments of the present disclosure, the q-axis current command I _q x, the d-axis current command I _d x, and the q-axis current command I _q x are calculated by the speed regulator 121, and the d-axis voltage command U _d x and the q-axis voltage command U _q ^* are obtained by the current regulator 122. The d-axis voltage command U _d and the q-axis voltage command U _q are input to the space vector pulse width modulation operation device 124 to perform driving control of the system by obtaining the α -axis voltage U _α (i.e., the first voltage) and the β -axis voltage U _β (i.e., the second voltage) through the inverse pek conversion device 123. The compensator 102 generates a first voltage compensation component Δu _α of the α -axis and a second voltage compensation component Δu _β of the β -axis of the motor according to the built-in adaptive stability control strategy, and superimposes the first voltage compensation component Δu _α on the first voltage U _α of the α -axis to form a first voltage command U _α, superimposes the second voltage compensation component Δu _β on the second voltage U _β of the β -axis, and superimposes the second voltage command U _β.

In this way, the influence of the harmonic wave on the air conditioner control system 10 can be reduced, so that the network side power quality is improved, and the stability of the air conditioner control system 10 is further improved.

In addition, I _a is an a-phase current in the three-phase stationary coordinate system, I _b is a b-phase current in the three-phase stationary coordinate system, and I _c is a c-phase current in the three-phase stationary coordinate system. I _α is the alpha-axis current (i.e., first current) in the two-phase stationary coordinate system, I _β is the beta-axis current (i.e., second current) in the two-phase stationary coordinate system, I _d is the direct-axis current setpoint,Is a DC feedback value. I _q is the quadrature current setpoint,Is the feedback value of the quadrature current. U _d is a given value of the direct-axis voltage in the two-phase rotation coordinate system, and U _q is a given value of the quadrature-axis voltage in the two-phase rotation coordinate system. U _α is the α -axis voltage output value (i.e., the first voltage) in the two-phase stationary coordinate system, and U _β is the β -axis voltage output value (i.e., the second voltage) in the two-phase stationary coordinate system. U _α is the α -axis voltage set point in the two-phase stationary coordinate system, and U _β is the β -axis voltage set point in the two-phase stationary coordinate system. Omega ^* _e is a motor rotation speed command, theta _e is a position angle of a rotor, and U _g is a switching signal for controlling the three-phase inverter generated by the space vector pulse width modulation operation device 124.

In some embodiments of the present disclosure, dual closed loop vector control subsystem 12 further includes a clark conversion device 128, clark conversion device 128 configured to convert currents I _a、I_b and I _c in a three-phase stationary coordinate system of motor 101 to currents I _a and I _β in a two-phase stationary coordinate system. From the stator perspective, I _a and I _β are mutually orthogonal time-generation current values.

In some embodiments of the present disclosure, the dual closed loop vector control subsystem 12 further includes a park transformation device 129, the park transformation device 129 configured to transform currents I _a and I _β in a two-phase stationary coordinate system to currents I _d and I _q in a two-phase rotating coordinate system. Note that I _d and I _q are orthogonal currents in a rotating coordinate system. Under steady state conditions, I _d and I _q are constants. The outputs U _d and U _q, i.e. the voltage vectors applied to the motor 101, are output by PI controllers. Further, a new angle θ _e is estimated by position estimation, and U _d and U _q outputted from the PI controller are inverse-transformed to orthogonal voltage values U _a and U _β in the stationary coordinate system by using the new angle θ _e, and then a new PWM duty value is calculated by the space vector pulse width modulation operation device 124 to generate a desired voltage vector.

In some embodiments of the present disclosure, the dual closed-loop vector control subsystem 12 further includes a position and speed observer 127, the position and speed observer 127 configured to resolve the rotation angle θ _e of the motor 101, the speed ω _e of the motor 101, and the motor speed command

Fig. 6 is a graph of current and voltage ripple spectra without superimposed compensation components according to some embodiments, and fig. 7 is a graph of current and voltage ripple spectra with superimposed compensation components according to some embodiments. Fig. 6 shows a-phase current I _a in the three-phase stationary coordinate system without superimposed compensation components, power-supply-phase input current iIN without superimposed compensation components, and bus voltage U without superimposed compensation components. Fig. 7 shows I _a after the compensation component is superimposed, the power supply phase input current iIN after the compensation component is superimposed, and the bus voltage U after the compensation component is superimposed.

As shown in fig. 6 and 7, as the power increases, the bus voltage U and the power phase input current iIN both decrease accordingly, which indicates that the network side power quality is improved, thereby improving the efficiency of the air conditioner control system 10 for using the power.

Fig. 8 is a block diagram of a compensator according to some embodiments, as shown in fig. 8, the compensator 102 includes a processor 301, and in some embodiments of the present disclosure, the compensator 102 further includes a memory 302 and a communication interface 303 coupled to the processor 301. Processor 301, memory 302, and communication interface 303 are coupled via bus 304.

Fig. 9 is a block diagram of still another air conditioning control system according to some embodiments, and as shown in fig. 9, some embodiments of the present disclosure further provide an air conditioning control system 20, wherein the air conditioning control system 20 is, for example, an electrolytic capacitor-less driving system 20, unlike the air conditioning control system 10 in fig. 5.

It should be noted that the electrolytic capacitor-less motor driving system 20 may be applied to various control systems, for example, may be applied to an air conditioning system. The air conditioning system comprises a multi-split air conditioning system.

Unlike the air conditioning control system 10, in some embodiments of the present disclosure, the electrolytic capacitor-less motor drive system 20 does not include the compensator 102. Unlike the three-phase thin film capacitive driver 125 in the dual closed loop vector control subsystem 12 of the air conditioning control system 10, the capacitive driver of the air conditioning control system 20 is a three-phase electroless capacitive driver 110, the three-phase electroless capacitive driver 110 being configured to implement variable frequency driving.

Furthermore, in some embodiments of the present disclosure, the capacitor-less motor drive system 20 further includes a first subtracting device 104, the first subtracting device 104 being configured to obtain the motor speed command and the rotational speed ω _e of the motor 101 that is analyzed by the position-and-rotational speed observer 127The difference of (a) is the rotational speed difference Δω _e, and the rotational speed difference Δω _e is output to the speed regulator 121.

In some embodiments of the present disclosure, the capacitor-less motor drive system 20 further includes a second subtracting device 105, the second subtracting device 105 being configured to command the current I _d in the two-phase rotating coordinate system obtained by the park converting device 129 and the current of the d-axis of the motor 101The subtraction results in a d-axis current difference Δi _d, and the d-axis current difference Δi _d is input to the current regulator 122.

In some embodiments of the present disclosure, the electrolytic capacitor-less motor driving system 20 further includes a third subtracting device 106, the third subtracting device 106 being configured to obtain the current I _q in the two-phase rotating coordinate system obtained by the change of the park converting device 129 and the current command of the q-axis of the motor 101I.e., the q-axis current difference Δi _q, and the q-axis current difference Δi _q is input to the current regulator 122.

In some embodiments of the present disclosure, the capacitor-less motor drive system 20 further includes a first summing device 107, the first summing device 107 configured to superimpose the first voltage compensation component Δu _α of the motor 101 on the first voltage U _α of the motor 101, generating a first voltage command for the α -axis

In some embodiments of the present disclosure, the capacitor-less motor drive system 20 further includes a second summing device 108, the second summing device 108 being configured to superimpose the second voltage compensation component Δu _β of the motor 101 on the second voltage U _β of the motor 101, generating a second voltage command for the β -axis

In some embodiments of the present disclosure, the electrolytic capacitor-less motor drive system 20 further includes an encoder 109, the encoder 109 being an optoelectronic encoder including a code wheel coupled to the rotor of the motor 101. The photoelectric encoder determines the current position of the code wheel by receiving the pulse signal, thereby measuring the operation position of the rotor of the motor 101, and thus the encoder 109 is configured to detect the operation position of the rotor of the motor 101.

In some embodiments of the present disclosure, the electrolytic capacitor-less motor driving system 20 further includes a comparator device 201, the comparator device 201 being configured to compare the common-frequency sawtooth wave U _sawtooth generated according to the LC resonance frequency with the sawtooth wave given value U _constant, resulting in a rectangular wave U _rectangular.

In some embodiments of the present disclosure, the magnitude of the on-channel sawtooth U _sawtooth is set to 1, for example, and the sawtooth given value U _constant is set to 0.8, for example. The comparator means 201 outputs 1 when the amplitude of the common-frequency sawtooth wave U _sawtooth is larger than the sawtooth wave given value U _constant, and outputs 0 when the amplitude of the common-frequency sawtooth wave U _sawtooth is smaller than the sawtooth wave given value U _constant, generating a rectangular wave U _rectangular having a duty ratio of 20% at the same frequency as the LC resonance frequency.

In some embodiments of the present disclosure, the electrolytic capacitor-less motor drive system 20 further includes a proportional amplification operation device 202, the proportional amplification operation device 202 being configured to amplify the rectangular wave U _rectangular, for example, to amplify the rectangular wave U _rectangular in equal proportion, to generate a given damping pulse at the same frequency as the LC resonance frequency

In some embodiments of the present disclosure, the amplification factor set by the scaling operation device 202 is, for example, 60, so that the adjustment stability is better while the adjustment speed of the rectangular wave equal-scale amplification is fast.

In some embodiments of the present disclosure, the capacitor-less motor drive system 20 further includes a time detection device 203, where the time detection device 203 is configured to perform time detection on the grid-side three-phase current, and obtain a time when the grid-side three-phase current is located at the trough.

In some embodiments of the present disclosure, the electrolytic capacitor-less motor drive system 20 further includes a phase operation device 204, the phase operation device 204 being configured to damp pulses according to the grid-side three-phase current pairsThe phase shift is performed to obtain the applied damping pulse U _pulse.

In some embodiments of the present disclosure, the phase computation device 204 damps the pulsesPhase shifting to damp the pulseThe medium-high level and the three-phase current on the net side are at the same moment when the three-phase current is at the trough.

In some embodiments of the present disclosure, the electrolytic capacitor-less motor drive system 20 further comprises a damping voltage generating device 205, the damping voltage generating device 205 being configured to derive a voltage compensation component Δu _α of the α -axis of the motor 101 and a voltage compensation component Δu _β of the β -axis of the motor from the applied damping pulse U _pulse.

In some embodiments of the present disclosure, the electrolytic capacitor-less motor driving system 20 further includes a controller 21, and the controller 21 refers to a device that can generate an operation control signal according to a command operation code and a timing signal, and instruct the electrolytic capacitor-less motor driving system 20 to execute a control command. The controller 21 may also be other devices with processing functions, such as a circuit, a device, or a software module, to which some embodiments of the present disclosure are not limited.

The controller 21 is coupled to control the components of the electrolytic capacitor-less motor drive system 20 and is configured to control the operation of the components of the electrolytic capacitor-less motor drive system 20 such that the electrolytic capacitor-less motor drive system 20 operates to perform its predetermined functions.

Fig.10 is a damping voltage generation unit diagram according to some embodiments, as shown in fig.10, in some embodiments of the present disclosure, if the voltage U _α >0 of the α -axis of the motor 101 is determined, the voltage compensation component Δu _α of the α -axis is the applied damping pulse U _pulse, and if the voltage U _α <0 of the α -axis of the motor 101 is determined, the voltage compensation component Δu _α of the α -axis is the negative number of the applied damping pulse U _pulse.

If the voltage U _β >0 on the beta-axis of the motor 101 is determined, the voltage compensation component Δu _β on the beta-axis is the negative number of the applied damping pulse U _pulse, and if the voltage U _β <0 on the beta-axis of the motor is determined, the voltage compensation component Δu _β on the beta-axis of the motor 101 is the applied damping pulse U _pulse.

Fig. 11 is a flowchart of yet another harmonic suppression method according to some embodiments, and some embodiments of the present disclosure provide a current harmonic suppression method of an electrolytic capacitor-less driving system 20, which is applied to a controller 21. As shown in fig. 11, the method includes S101 to S106.

S101, acquiring the same-frequency sawtooth wave.

The same frequency sawtooth wave U _sawtooth is generated according to the LC resonance frequency, so the same frequency sawtooth wave U _sawtooth has the same frequency as the LC resonance frequency.

Fig. 12 is a waveform diagram of an on-channel sawtooth waveform, as shown in fig. 12, in which the waveform of the on-channel sawtooth waveform U _sawtooth periodically rises in an inclined straight line and falls in a straight line perpendicular to the transverse axis, and is a non-sinusoidal waveform, according to some embodiments.

S102, comparing the same-frequency sawtooth wave with a sawtooth wave given value to obtain a rectangular wave, and amplifying the rectangular wave to obtain a given damping pulse.

Fig. 13 is a waveform diagram of a common-frequency sawtooth wave given value, as shown in fig. 13, where the sawtooth wave given value may be a preset fixed value when the electrolytic capacitor-less driving system 20 leaves the factory, and the amplitude of the sawtooth wave given value is not changed.

In some embodiments of the present disclosure, a high level is output when the magnitude of the on-channel sawtooth U _sawtooth is greater than the sawtooth given value U _constant, and a low level is output when the magnitude of the on-channel sawtooth U _sawtooth is less than the sawtooth given value U _constant. Thus, by comparing the same-frequency sawtooth wave U _sawtooth with the sawtooth wave given value U _constant, a rectangular wave U _rectangular having the same frequency as the same-frequency sawtooth wave U _sawtooth can be obtained.

Fig. 14 is a waveform diagram of a rectangular wave according to some embodiments, as shown in fig. 14, in which the waveform of the rectangular wave U _rectangular obtained by comparing the common-frequency sawtooth wave U _sawtooth with the sawtooth wave given value U _constant periodically rises in a straight line perpendicular to the transverse axis and falls in a straight line perpendicular to the transverse axis, and the waveform is rectangular and is a non-sinusoidal wave.

In some embodiments of the present disclosure, after the rectangular wave U _rectangular is obtained, it may be input into the proportional amplifying operation device 202, and the proportional amplifying operation device 202 performs equal-proportion amplification on the rectangular wave U _rectangular to obtain a given damping pulse

It will be appreciated that equal proportional amplification of rectangular wave U _rectangular may have sufficient damping pulses.

For example, when the amplitude of the common-frequency sawtooth wave U _sawtooth is set to 1 and the sawtooth wave given value U _constant is set to 0.8, a high level is output when the amplitude of the common-frequency sawtooth wave U _sawtooth is greater than 0.8, and when the amplitude of the common-frequency sawtooth wave U _sawtooth is less than 0.8, a low level is output, and by comparing the common-frequency sawtooth wave with the sawtooth wave given value, a rectangular wave U _rectangular having a duty ratio of 20% can be obtained. Then amplifying rectangular wave U _rectangular by 60 times to obtain given damping pulse

In some embodiments of the present disclosure, the proportional amplifying operation device 202 performs equal proportional amplification on the rectangular wave U _rectangular, and obtains a given damping pulseAfter that, the damping pulse is givenTo the phase operation device 204. Correspondingly, the phase operation device 204 receives the constant damping pulse

And S103, performing phase shift on the given damping pulse according to the three-phase current at the net side to obtain the applied damping pulse. Wherein, the three-phase current at the net side is sinusoidal alternating current. The sinusoidal alternating current is a current which changes with time and is changed according to a sine function rule, and the sinusoidal alternating current has wave crests and wave troughs.

Fig. 15 is a flow chart of yet another harmonic suppression method according to some embodiments, as shown in fig. 15, in some embodiments of the present disclosure, S103 may include S1031 and S1032.

S1031, detecting the time of the three-phase current at the net side to obtain the time when the three-phase current at the net side is positioned at the trough.

In some embodiments of the present disclosure, the time detection device 203 obtains the net side three-phase currents I _u、I_v and I _w, and performs time detection on the net side three-phase currents to obtain the time when the net side three-phase currents are located at the trough, for a given damping pulseAnd (5) adjusting.

In some embodiments of the present disclosure, after the time detection device 203 obtains the time when the grid-side three-phase current is located at the trough, the time when the grid-side three-phase current is located at the trough is transmitted to the phase operation device 204. Accordingly, the phase operation device 204 receives the time when the three-phase current on the net side is located at the trough.

S1032, carrying out phase shift on the given damping pulse according to the time when the three-phase current at the net side is at the trough, and obtaining the applied damping pulse.

In some embodiments of the present disclosure, the phase computation device 204 counts the time that the net side three-phase current is at the trough for a given damping pulsePhase shifting, giving damping pulsesThe time at the high level is shifted to coincide with the time at which the net side three-phase current is at the trough, resulting in the applied damping pulse U _pulse.

And S104, obtaining an alpha-axis voltage compensation component (namely a first voltage compensation component delta U _α) and a beta-axis voltage compensation component (namely a second voltage compensation component delta U _β) according to the applied damping pulse.

The controller 21 can obtain an α -axis voltage compensation component and a β -axis voltage compensation component through the applied damping pulse U _pulse, and can reduce the influence of harmonics on the electrolytic capacitor-less driving system 20 by respectively superimposing the α -axis voltage compensation component and the β -axis voltage compensation component on the α -axis voltage and the β -axis voltage, thereby improving the network-side power quality.

Fig. 16 is a flow chart of yet another harmonic suppression method according to some embodiments, as shown in fig. 16, in some embodiments of the present disclosure, S104 may include S1041 and S1042.

S1041, obtaining an alpha-axis voltage compensation component according to the applied damping pulse and the alpha-axis voltage.

The damping voltage generating device 205 acquires the applied damping pulse, the α -axis voltage, and the preset voltage, and obtains an α -axis voltage compensation component from the applied damping pulse, the α -axis voltage, and the preset voltage. The preset voltage is preset at the time of shipping the electrolytic capacitor-less driving system 20, and is, for example, 0.

In some embodiments of the present disclosure, after the damping voltage generating device 205 obtains the α -axis voltage U _α and the preset voltage, the α -axis voltage U _α is compared with the preset voltage, if it is determined that the α -axis voltage U _α is greater than the preset voltage, the α -axis voltage compensation component Δu _α is the negative number of the applied damping pulse U _pulse, if it is determined that the α -axis voltage U _α is less than the preset voltage, the α -axis voltage compensation component Δu _α is the applied damping pulse U _pulse, and the α -axis voltage compensation component Δu _α is applied to the first adding device 107.

S1042, obtaining a beta-axis voltage compensation component according to the applied damping pulse and the beta-axis voltage.

The damping voltage generating device 205 acquires the applied damping pulse, the voltage of the β axis, and the preset voltage, and obtains the voltage compensation component of the β axis from the applied damping pulse, the voltage of the β axis, and the preset voltage.

In some embodiments of the present disclosure, after the damping voltage generating device 205 obtains the β -axis voltage U _β and the preset voltage, the β -axis voltage U _β is compared with the preset voltage, if it is determined that the β -axis voltage U _β is greater than the preset voltage, the β -axis voltage compensation component Δu _β is determined to be the negative number of the applied damping pulse U _pulse, if it is determined that the β -axis voltage U _β is less than the preset voltage, the β -axis voltage compensation component Δu _β is determined to be the applied damping pulse U _pulse, and the β -axis voltage compensation component Δu _β is applied to the second adding device 108.

It should be noted that, some embodiments of the present disclosure do not limit the execution sequence of S1041 and S1042. For example, step S1041 may be performed first and then S1042 may be performed, for example, S1042 may be performed first and then S1041 may be performed, and for example, S1041 and S1042 may be performed simultaneously.

S105, superposing the alpha-axis voltage compensation component on the alpha-axis voltage to obtain an alpha-axis voltage command U _α (namely a first voltage command), and superposing the beta-axis voltage compensation component on the beta-axis voltage to obtain a beta-axis voltage command U _β (namely a second voltage command).

It will be appreciated that due to the alpha-axis voltage commandIs obtained by superposing the alpha-axis voltage U _α with the compensation component delta U _α, and the alpha-axis voltage commandCompared with U _α which is less affected by harmonic wave and has higher voltage quality, the same beta-axis voltage commandThe voltage quality is higher compared to the beta-axis voltage U _β, which is less affected by harmonics.

S106, the α -axis voltage command and the β -axis voltage command are applied to the space vector pulse width modulation operation device 124.

In some embodiments of the present disclosure, the controller 21 inputs the α -axis voltage command and the β -axis voltage command as parameters of the electrolytic capacitor-less driving system to the space vector pulse width modulation operation device 124. In this way, LC resonance phenomenon existing in the input current and the bus voltage can be reduced, the harmonic wave of the network side input current is reduced, the power of the electrolytic capacitor-free driving system 20 is increased, the network side input quality of the electrolytic capacitor-free driving system 20 is ensured, and the influence on the network side current is avoided.

Fig. 17 is a flowchart of yet another harmonic suppression method according to some embodiments, as shown in fig. 17, after the electrolytic capacitor-less driving system 20 is operated, the comparator device 201 obtains the same-frequency sawtooth wave and the sawtooth wave given value, compares the same-frequency sawtooth wave with the sawtooth wave given value, outputs a high level when the amplitude of the same-frequency sawtooth wave is greater than the sawtooth wave given value, and outputs a low level when the amplitude of the same-frequency sawtooth wave is less than the given value. Thus, a rectangular wave having the same frequency as the LC resonance frequency is obtained by comparing the same-frequency sawtooth wave with the sawtooth wave given value, and the rectangular wave is output to the proportional amplifying operation device 202. The proportional amplification operation device 202 amplifies the rectangular wave after obtaining the rectangular wave, obtains a given damping pulse, and outputs the damping pulse to the phase operation device 204.

The time detection device 203 performs time detection on the net side three-phase current, obtains the time when the net side three-phase current is located at the trough, and outputs the time to the phase operation device 204. After acquiring the timing at which the net side three-phase current is located at the trough and the given damping pulse, the phase operation device 204 performs phase shift on the given damping pulse according to the timing at which the net side three-phase current is located at the trough, so that the timing of the high level in the given damping pulse coincides with the timing at which the net side three-phase current is located at the trough, and obtains the applied damping pulse, and outputs the damping pulse to the damping voltage generation device 205.

After the damping voltage generating device 205 obtains the α -axis voltage, the β -axis voltage, and the applied damping pulse, an α -axis voltage compensation component is obtained according to the applied damping pulse and the α -axis voltage, and when the α -axis voltage is greater than the preset voltage, the α -axis voltage compensation component is the negative number of the applied damping pulse, and when the α -axis voltage is less than the preset voltage, the α -axis voltage compensation component is the applied damping pulse. After the α -axis voltage compensation component is obtained, the α -axis voltage compensation component is output to the first adder 107. And obtaining a beta-axis voltage compensation component according to the applied damping pulse and the beta-axis voltage, wherein the beta-axis voltage compensation component is the negative number of the applied damping pulse when the beta-axis voltage is larger than a preset voltage, and is the applied damping pulse when the beta-axis voltage is smaller than the preset voltage. After the β -axis voltage compensation component is obtained, the β -axis voltage compensation component is output to the second adder 108.

The first addition means 107 obtains the α -axis voltage and the α -axis voltage compensation component, superimposes the α -axis voltage compensation component on the α -axis voltage to obtain an α -axis voltage command, and applies the α -axis voltage command to the space vector pulse width modulation calculation means 124, and the second addition means 108 obtains the β -axis voltage and the β -axis voltage compensation component, superimposes the β -axis voltage compensation component on the β -axis voltage to obtain a β -axis voltage command, and applies the β -axis voltage command to the space vector pulse width modulation calculation means 124.

Fig. 18 is a block diagram of a controller according to some embodiments, and as shown in fig. 18, in some embodiments 2 of the present disclosure, the controller 21 includes an acquisition component 1001, a comparator component 1002, an amplification operation component 1003, a phase operation component 1004, a damping voltage generation component 1005, a first addition operation component 1006, and a second addition operation component 1007.

The acquisition component 1001 is configured to acquire the on-channel sawtooth wave U _sawtooth.

The comparator component 1002 is configured to compare the common frequency sawtooth wave U _sawtooth to a sawtooth wave given value U _constant to produce a rectangular wave U _rectangular.

The amplifying operation assembly 1003 is configured to amplify the rectangular wave U _rectangular to obtain a given damping pulse

The phase computation component 1004 is configured to give damping pulses according to the grid-side three-phase currentThe phase shift is performed to obtain the applied damping pulse U _pulse.

The damping voltage generating component 1005 is configured to obtain an α -axis voltage compensation component Δu _α and a β -axis voltage compensation component Δu _β according to the applied damping pulse U _pulse.

The first adder 1006 is configured to superimpose the alpha-axis voltage compensation component Δu _α on the alpha-axis voltage U _α to obtain an alpha-axis voltage commandCommanding an alpha axis voltageOutput to the space vector pwm operation device 124.

The second adder 1007 is configured to superimpose the beta-axis voltage compensation component Δu _β on the beta-axis voltage U _β to obtain a beta-axis voltage commandCommanding beta-axis voltageOutput to the space vector pwm operation device 124.

Fig. 19 is a hardware architecture diagram of a controller according to some embodiments, as shown in fig. 19, in other embodiments of the present disclosure, the controller 21 includes a processor 3001, and in some embodiments of the present disclosure, the controller 21 further includes a memory 3002 and a communication interface 3003 coupled to the processor 3001. The processor 3001, memory 3002, and communication interface 3003 are coupled by bus 3004.

Some embodiments of the present disclosure also provide a computer-readable storage medium comprising computer-executable instructions that, when run on a computer, cause the computer to perform any one of the methods provided by the above embodiments.

Some embodiments of the present disclosure also provide a computer program product comprising computer-executable instructions which, when run on a computer, cause the computer to perform any one of the methods provided by the above embodiments.

Some embodiments of the present disclosure also provide a chip comprising a processor and an interface, the processor being coupled to the memory through the interface, the processor, when executing a computer program or computer-executable instructions in the memory, causing the computer to perform any one of the methods provided by the embodiments above.

Those skilled in the art will appreciate that the scope of the disclosure of the present disclosure is not limited to the specific embodiments described above, and that modifications and substitutions of certain elements of the embodiments may be made without departing from the spirit of the disclosure. The scope of the present disclosure is limited by the appended claims.

Claims (20)

1. An air conditioner control system, comprising:

   An inverse pek transformer configured to output a first voltage and a second voltage;

   a motor coupled with the inverse pekine converter, the motor comprising a first shaft and a second shaft;

   The first voltage is input to the first shaft and the second voltage is input to the second shaft;

   a compensator configured to:

   Determining a target damping coefficient and a first damping power, wherein the target damping coefficient is obtained based on the equivalent power of the motor and the direct current component of the bus voltage thereof;

   determining a second damping power based on the target damping coefficient and the first damping power;

   Based on the second damping power, the first current of the first shaft, and the second current of the second shaft, a first voltage compensation component of the first shaft and a second voltage compensation component of the second shaft are determined, and the first voltage compensation component is superimposed to the first voltage, and the second voltage compensation component is superimposed to the second voltage, respectively, to suppress harmonics.
2. The air conditioner control system of claim 1, wherein the determining a target damping coefficient comprises:

   And determining the quotient of the equivalent power of the motor and the square of the direct current component as the target damping coefficient.
3. The air conditioner control system of claim 1 or 2, wherein the determining a second damping power based on the target damping coefficient and the first damping power comprises:

   And determining the product of the target damping coefficient and the first damping power as the second damping power.
4. The air conditioner control system of any one of claims 1 to 3, wherein the determining a first voltage compensation component of the first shaft and a second voltage compensation component of the second shaft, respectively, based on the second damping power, a first current of the first shaft, and a second current of the second shaft, comprises:

   Multiplying the second damping power by the first current to obtain a first value, and adding the square of the first current to the square of the second current to obtain a second value;

   Determining a quotient of the first value and the second value as the first voltage compensation component;

   Multiplying the second damping power by the second current to obtain a third value;

   determining the quotient of the third value and the second value as the second voltage compensation component.
5. The air conditioner control system of any one of claims 1-4, wherein the determining the first damping power comprises:

   and determining the fluctuation component through a preset band-pass filtering algorithm, and determining the product of the fluctuation component and the bus voltage as the first damping power.
6. The air conditioner control system of any one of claims 1 to 4, wherein the compensator is further configured to determine the direct current component by a preset low pass filtering algorithm.
7. The air conditioner control system of any one of claims 1 to 4, wherein the motor is a permanent magnet synchronous motor.
8. The air conditioner control system of any one of claims 1 to 4, wherein the first axis is an alpha axis and the second axis is a beta axis.
9. An air conditioner control system, comprising:

   a comparator device configured to compare the same-frequency sawtooth wave with a given value of the sawtooth wave to obtain a rectangular wave;

   The proportional amplification operation device is coupled with the comparator device and is configured to amplify the rectangular wave to obtain a given damping pulse;

   The phase operation device is coupled with the proportional amplification operation device and is configured to perform phase shift on the given damping pulse according to the three-phase current on the network side to obtain an applied damping pulse;

   Damping voltage generating means, coupled to the phase operation means, configured to derive a first voltage compensation component and a second voltage compensation component from the applied damping pulse;

   The first addition operation device is coupled with the damping voltage generation device and is configured to superimpose the first voltage compensation component on a first voltage to obtain a first voltage instruction, and the first voltage instruction is output to the space vector pulse width modulation operation device;

   The second addition operation device is coupled with the damping voltage generation device and is configured to superimpose the second voltage compensation component on a second voltage to obtain a second voltage instruction, and the second voltage instruction is output to the space vector pulse width modulation operation device;

   And a controller coupled to the comparator device, the proportional amplifying operation device, the phase operation device, the damping voltage generation device, the first addition operation device and the second addition operation device, and configured to acquire the same-frequency sawtooth wave, wherein the same-frequency sawtooth wave is generated according to LC resonance frequency.
10. The air conditioner control system of claim 9, wherein,

    The phase operation device is configured to perform time detection on the grid-side three-phase current to obtain time when the grid-side three-phase current is located at a trough, and perform phase movement on the given damping pulse according to time when the grid-side three-phase current is located at the trough to obtain the applied damping pulse.
11. The air conditioner control system as claimed in claim 9 or 10, wherein,

    The damping voltage generating device is configured to obtain the first voltage compensation component according to the applied damping pulse and a first voltage;

    And obtaining the second voltage compensation component according to the applied damping pulse and the second voltage.
12. The air conditioner control system according to any one of claims 9 to 11, wherein,

    The damping voltage generating device is further configured to:

    If the first voltage is determined to be greater than a preset voltage, the first voltage compensation component is the negative number of the applied damping pulse;

    If the first voltage is determined to be smaller than the preset voltage, the first voltage compensation component is the applied damping pulse;

    If the second voltage is determined to be greater than the preset voltage, the second voltage compensation component is the negative number of the applied damping pulse;

    And if the second voltage is determined to be lower than the preset voltage, the second voltage compensation component is the applied damping pulse.
13. A harmonic suppression method of an air conditioning control system, wherein the air conditioning system comprises:

    An inverse pek transformer configured to output a first voltage and a second voltage;

    A motor coupled to the inverse pek transformer and the compensator, respectively, the motor including a first shaft and a second shaft;

    The first voltage is input to the first shaft and the second voltage is input to the second shaft;

    a compensator coupled to the inverse pek transformer and the motor;

    the harmonic suppression method comprises the following steps:

    Determining a target damping coefficient and a first damping power, wherein the target damping coefficient is obtained based on the equivalent power of the motor and the direct current component of the bus voltage, and the first damping power is configured to represent the power of the fluctuation component of the bus voltage;

    determining a second damping power based on the target damping coefficient and the first damping power;

    A first voltage compensation component of the first shaft and a second voltage compensation component of the second shaft are determined based on the second damping power, the first current of the first shaft, and the second current of the second shaft, respectively, and the first voltage compensation component is superimposed to the first voltage and the second voltage compensation component is superimposed to the second voltage.
14. The harmonic suppression method of claim 13, wherein the determining a target damping coefficient comprises:

    determining the quotient of the equivalent power and the square of the direct current component as the target damping coefficient.
15. An air conditioner control system harmonic suppression method, wherein the air conditioner control system comprises:

    A comparator device;

    A proportional amplifying operation device coupled with the comparator device;

    the phase operation device is coupled with the proportional amplification operation device;

    damping voltage generating device coupled with the phase operation device;

    A first adder coupled to the damping voltage generator;

    A second addition means coupled to the damping voltage generation means;

    A controller coupled to the comparator means, the proportional amplifying means, the phase means, the damping voltage generating means, the first adding means, and the second adding means;

    the harmonic suppression method comprises the following steps:

    The method comprises the steps of obtaining same-frequency sawtooth waves, wherein the same-frequency sawtooth waves are generated according to LC resonance frequency;

    Comparing the same-frequency sawtooth wave with a sawtooth wave given value to obtain a rectangular wave, and amplifying the rectangular wave to obtain a given damping pulse;

    performing phase shift on the given damping pulse according to the three-phase current at the network side to obtain an applied damping pulse;

    Obtaining a first voltage compensation component and a second voltage compensation component according to the applied damping pulse;

    superposing the first voltage compensation component on a first voltage to obtain a first voltage instruction;

    superposing the second voltage compensation component on a second voltage to obtain a second voltage instruction;

    the first voltage command and the second voltage command are applied to a space vector pulse width modulation operation device.
16. The method of claim 15, wherein said phase shifting the given damping pulse from the net side three phase current results in an applied damping pulse, comprising:

    Performing time detection on the three-phase current of the grid side to obtain the time when the three-phase current of the grid side is positioned at the trough;

    And carrying out phase shift on the given damping pulse according to the time when the three-phase current on the net side is at the trough, so as to obtain the applied damping pulse.
17. The method of claim 15, wherein the deriving a first voltage compensation component and a second voltage compensation component from the applied damping pulse comprises:

    obtaining the first voltage compensation component according to the applied damping pulse and the first voltage;

    And obtaining the second voltage compensation component according to the applied damping pulse and the second voltage.
18. The method of claim 17, wherein the deriving the first voltage compensation component from the applied damping pulse and a first voltage comprises:

    If the first voltage is determined to be greater than a preset voltage, the first voltage compensation component is the negative number of the applied damping pulse;

    And if the first voltage is determined to be smaller than the preset voltage, the first voltage compensation component is the applied damping pulse.
19. The method of claim 17, wherein said deriving the second voltage compensation component from the applied damping pulse and a second voltage comprises:

    if the second voltage is determined to be greater than a preset voltage, the second voltage compensation component is the negative number of the applied damping pulse;

    And if the second voltage is determined to be lower than the preset voltage, the second voltage compensation component is the applied damping pulse.
20. A computer readable storage medium comprising computer instructions which, when run on a computer, cause the computer to perform the method of any one of claims 13 to 19.