CN120128445A

CN120128445A - A communication method and device

Info

Publication number: CN120128445A
Application number: CN202311684424.XA
Authority: CN
Inventors: 马千里; 黄煌
Original assignee: Huawei Technologies Co Ltd
Current assignee: Huawei Technologies Co Ltd
Priority date: 2023-12-07
Filing date: 2023-12-07
Publication date: 2025-06-10
Also published as: WO2025118929A1

Abstract

The embodiment of the present application discloses a communication method and device, the method comprising: generating a first signal, the first signal comprising a first signal and a second signal, the first signal comprising X first data signals, the first data signal being The second signal path includes Y second data signals and M first phase noise tracking pilot signals PTRS, and the second data signal is The first PTRS is The _θ1 belongs to [0,2π), the _θ2 belongs to [0,2π), The M first PTRS are used to process phase noise, the first signal and the second signal are continuously interleaved, X, Y, M and N are all integers greater than or equal to 1, and a, b and c are all real numbers; the first signal is sent to the terminal device. By adopting the embodiment of the present application, the accuracy of phase noise processing can be improved and the communication performance can be improved.

Description

Communication method and device

Technical Field

The present application relates to the field of communications technologies, and in particular, to a communications method and apparatus.

Background

The signals of the wireless communication system are transmitted to a remote place, and the orthogonal frequency division multiplexing power amplification is required. Due to technical and cost constraints, a power amplifier tends to be linearly amplified only in a range beyond which signal distortion can result. Signal distortion can cause the receiver to fail to properly parse the signal. In order to ensure that the signal peaks remain within the linear range of the power amplifier, the average power must be reduced, which may lead to inefficiency or equivalently reduced coverage of the power amplifier. To meet the coverage requirements, a signal generation technique with a low peak-to-average power ratio (peak to average power ratio, PAPR) is often selected.

In the technical field, single carrier-offset quadrature amplitude modulation (SINGLE CARRIER-Offset quadrature amplitude modulation, SC-OQAM) and single carrier transform spread orthogonal frequency division multiplexing (discrete fourier transform spread orthogonal frequency division multiplexing, DFT-s-OFDM with FTSS) can reduce the PAPR of the discrete fourier transform spread orthogonal frequency division multiplexing (discrete fourier transform spreading orthogonal frequency division multiplexing, DFT-s-OFDM) waveform, and are alternative waveform technologies in future mobile communication and high frequency scenarios. However, when the modulation mode of the transmitted signal is changed from the conventional quadrature amplitude modulation (quadrature amplitude modulation, QAM) constellation point to the OQAM or DFT-S-OFDM with FTSS with low PAPR, the phase noise cannot be estimated by the separation of the real part and the imaginary part, and the communication performance is affected.

Disclosure of Invention

The embodiment of the application provides a communication method and a communication device, which can improve the accuracy of phase noise processing and the communication performance.

In a first aspect, an embodiment of the present application provides a communication method, where the method is applied to a network device, or a chip or a circuit configured in the network device, and includes:

generating a first signal, wherein the first signal comprises a first path of signals and a second path of signals, the first path of signals comprises X first data signals, and the first data signals are The second path signal comprises Y second data signals and M first phase noise tracking pilot signals PTRS, wherein the second data signals areThe first PTRS isThe θ ₁ belongs to [0,2π), the θ ₂ belongs to [0,2π),The M first PTRS are used for processing phase noise, the first path of signals and the second path of signals are continuously interleaved, X, Y, M and N are integers which are larger than or equal to 1, a, b and c are real numbers, and the first signals are sent to terminal equipment.

Through the continuous interweaving arrangement of the first path of signals and the second path of signals, the phase angle between the first path of signals and the second path of signals meets the following conditionsAnd a first PTRS for processing phase noise is set in the second signal. For example, the first path of signal is a real signal, and a real pilot signal is set at a position where an imaginary signal is originally set in the second path of signal, so that interference of data carried by the first signal on the first PTRS is in the same direction as the first PTRS, and signal energy of the first PTRS is maximized. Thus, the first PTRS is utilized to process the phase noise, the accuracy of the phase noise processing is improved, and the communication performance is improved.

In one possible design, the positive and negative phases of the first PTRS are determined from the positive and negative phases of the interference of the data carried by the first signal to the first PTRS. The positive phase and the negative phase of the first PTRS are determined through the positive phase and the negative phase of the interference of the data carried by the first signal on the first PTRS, so that the maximum energy of the first PTRS is ensured, the first PTRS is utilized to process the phase noise, and the accuracy of the phase noise processing is improved.

In one possible design, the positive and negative phases of the first PTRS are determined from the positive and negative phases of the interference of the data carried by the first signal to the first PTRS. The positive phase and the negative phase of the first PTRS are determined through the positive phase and the negative phase of the interference of the data carried by the first signal on the first PTRS, so that the signal energy of the transmitted PTRS can be reduced, the signal energy of the first PTRS is reduced when the capability of the receiving end for processing phase noise is not changed, and the signal energy of the data is improved, because the total energy is constant.

In one possible design, the positive and negative phases of the first PTRS are the same as the positive and negative phases of the interference of the data carried by the first signal on the first PTRS. The energy of the first PTRS is maximized, so that the first PTRS is utilized to process the phase noise, and the accuracy of the phase noise processing is improved.

In one possible design, the first path signal further includes M second PTRS, one corresponding to each of the first PTRS, where the second PTRS isThe M second PTRSs are used for carrying data, and d is a real number. And the second PTRS is used for carrying constellation symbols so as to carry more bits, so that the efficiency of data transmission is ensured.

In one possible design, the positive and negative phases of the second PTRS are the same as the positive and negative phases of the first PTRS. The positive and negative phases of the interference of the second PTRS to the first PTRS are the same as the positive and negative phases of the first PTRS, so that the energy of the first PTRS is maximum.

In one possible design, the second PTRS is adjacent to the first PTRS. Thereby facilitating the adjustment of the positive and negative phases of the second PTRS in the first path signal so as to more closely match the effect on the first PTRS in the second path signal.

In one possible design, the M first PTRS are equally spaced in the second signal. So that the data carried by the first signal is consistent with the effects of the plurality of first PTRSs. For example, the interference of the data carried by the first signal to the plurality of first PTRSs is positive phase.

In one possible design, a predefined PTRS pattern is sent to the terminal device, which is used to determine PTRS parameters. The method comprises the steps that a terminal device determines PTRS parameters corresponding to a PTRS pattern according to a current scheduling bandwidth, a mapping position of a first PTRS in a first signal is determined based on the PTRS parameters, the first PTRS is obtained at the mapping position in the first signal, and phase noise is processed through the first PTRS.

In a second aspect, an embodiment of the present application provides a communication method, where the method is applied to a terminal device, or a chip or a circuit configured in the terminal device, and includes:

Receiving a first signal sent by network equipment, wherein the first signal comprises a first path of signal and a second path of signal, the first path of signal comprises X first data signals, and the first data signals are The second path signal comprises Y second data signals and M first phase noise tracking pilot signals PTRS, wherein the second data signals areThe first PTRS isThe θ ₁ belongs to [0,2π), the θ ₂ belongs to [0,2π),The M first PTRSs are used for processing phase noise, the first path of signals and the second path of signals are continuously interleaved, X, Y, M and N are integers which are larger than or equal to 1, a, b and c are real numbers, and the phase noise is processed based on the M first PTRSs, so that communication performance is improved.

Through the continuous interweaving arrangement of the first path of signals and the second path of signals, the phase angle between the first path of signals and the second path of signals meets the following conditionsAnd a first PTRS for processing phase noise is set in the second signal. For example, the first path of signal is a real signal, and a real pilot signal is set at a position where an imaginary signal is originally set in the second path of signal, so that interference of data carried by the first signal on the first PTRS is in the same direction as the first PTRS, and signal energy of the first PTRS is maximized. Thus, the first PTRS is utilized to process the phase noise, and the accuracy of the phase noise processing is improved.

In one possible design, a predefined PTRS pattern sent by the network device is received, the PTRS pattern being used to determine PTRS parameters. And determining the mapping position of the first PTRS in the first signal through the PTRS parameter so as to acquire the first PTRS at the mapping position in the first signal, and processing the phase noise through the first PTRS.

In a third aspect, an embodiment of the present application provides a communication apparatus, including:

the processing module is used for generating a first signal, wherein the first signal comprises a first path of signal and a second path of signal, the first path of signal comprises X first data signals, and the first data signals are The second path signal comprises Y second data signals and M first phase noise tracking pilot signals PTRS, wherein the second data signals areThe first PTRS isThe θ belongs to [0,2π), the θ ₂ belongs to [0,2π),The M first PTRS are used for processing phase noise, the first path of signals and the second path of signals are continuously interleaved, X, Y, M and N are integers which are more than or equal to 1, and a, b and c are real numbers;

And the sending module is used for sending the first signal to the terminal equipment.

In one possible design, the positive and negative phases of the first PTRS are determined from the positive and negative phases of the interference of the data carried by the first signal to the first PTRS.

In one possible design, the positive and negative phases of the first PTRS are the same as the positive and negative phases of the interference of the data carried by the first signal on the first PTRS.

In one possible design, the first path signal further includes M second PTRS, one corresponding to each of the first PTRS, where the second PTRS isThe M second PTRSs are used for carrying data, and d is a real number.

In one possible design, the positive and negative phases of the second PTRS are the same as the positive and negative phases of the first PTRS.

In one possible design, the second PTRS is adjacent to the first PTRS.

In one possible design, the M first PTRS are equally spaced in the second signal.

In one possible design, the transmitting module is further configured to transmit a predefined PTRS pattern to the terminal device, where the PTRS pattern is used to determine PTRS parameters.

In a fourth aspect, an embodiment of the present application provides a communication apparatus, including:

The receiving module is configured to receive a first signal sent by a network device, where the first signal includes a first path of signal and a second path of signal, the first path of signal includes X first data signals, and the first data signals are The second path signal comprises Y second data signals and M first phase noise tracking pilot signals PTRS, wherein the second data signals areThe first PTRS isThe θ ₁ belongs to [0,2π), the θ ₂ belongs to [0,2π),The M first PTRS are used for processing phase noise, the first path of signals and the second path of signals are continuously interleaved, X, Y, M and N are integers which are more than or equal to 1, and a, b and c are real numbers;

and the processing module is used for processing the phase noise based on the M first PTRS.

In one possible design, the second PTRS is adjacent to the first PTRS.

In one possible design, the receiving module is further configured to receive a predefined PTRS pattern sent by the network device, where the PTRS pattern is used to determine a PTRS parameter.

In a fifth aspect, the present application provides a communications apparatus comprising a processor and a memory for storing a computer program, the processor being configured to execute the computer program stored in the memory to cause the communications apparatus to perform the method according to any one of the first aspects.

In a sixth aspect, the present application provides a communications apparatus comprising a processor and a memory, the memory configured to store a computer program, the processor configured to execute the computer program stored in the memory, to cause the communications apparatus to perform the method of any one of the second aspects.

In a seventh aspect, the present application provides a communication apparatus, which may be a network device, or an apparatus in a network device, or an apparatus that can be used in cooperation with a network device. The communication device may also be a chip system. The communication device may perform the method of the first aspect. The functions of the communication device can be realized by hardware, and can also be realized by executing corresponding software by hardware. The hardware or software includes one or more modules corresponding to the functions described above. The module may be software and/or hardware. The operations and advantages performed by the communication device may be referred to the methods and advantages described in the first aspect, and the repetition is not repeated.

In an eighth aspect, the present application provides a communication apparatus, which may be a terminal device, or an apparatus in a terminal device, or an apparatus that can be used in a matching manner with a terminal device. The communication device may also be a chip system. The communication device may perform the method of the second aspect. The functions of the communication device can be realized by hardware, and can also be realized by executing corresponding software by hardware. The hardware or software includes one or more modules corresponding to the functions described above. The module may be software and/or hardware. The operations and advantages performed by the communication device may be referred to the methods and advantages described in the second aspect, and the repetition is omitted.

In a ninth aspect, the present application provides a computer readable storage medium for storing a computer program which, when executed, causes the method of any one of the first and second aspects to be implemented.

In a tenth aspect, the present application provides a computer program product comprising a computer program which, when executed, causes the method according to any one of the first and second aspects to be carried out.

In an eleventh aspect, an embodiment of the present application provides a communication system, which includes at least one terminal device and at least one network device, where the network device is configured to perform the steps in the first aspect, and the terminal device is configured to perform the steps in the second aspect.

In a twelfth aspect, a chip is provided, the chip comprising a processor and a communication interface for communicating with an external device or an internal device, the processor being configured to implement the methods of the above aspects.

In one possible design, the chip may further include a memory having stored therein a computer program or instructions, the processor for executing the computer program or instructions stored in the memory, or derived from other programs or instructions. The computer program or instructions, when executed, is operable to perform the methods of the various aspects described above.

In one possible design, the chip may be integrated on a terminal device or a network device.

Drawings

Fig. 1 is a schematic structural diagram of a communication system according to an embodiment of the present application;

FIG. 2 is a schematic diagram of peak and average power;

FIG. 3 is a schematic diagram of an OFDM amplitude;

FIG. 4 is a schematic diagram of the effect of phase noise on a received signal;

FIG. 5 is a schematic diagram of a process flow of a DFT-s-OFDM technique;

FIG. 6 is a schematic diagram of SC-OQAM signal processing;

FIG. 7 is a schematic diagram of SC-QAM signal processing;

FIG. 8 is a schematic diagram of an SC-QAM waveform;

FIG. 9 is a schematic diagram of an SC-OQAM waveform;

FIG. 10 is a schematic diagram of DFT-S-OFDM with FTSS signal processing;

FIG. 11 is a schematic diagram of the filtering of DFT-S-OFDM with FTSS;

FIG. 12 is a schematic illustration of a PTRS pattern for DFT-s-OFDM;

FIG. 13 is a schematic diagram of a filter's waveform disturbance;

FIG. 14 is a schematic diagram of a performance comparison;

fig. 15 is a schematic flow chart of a communication method according to an embodiment of the present application;

FIG. 16 is a schematic diagram of a first signal;

FIG. 17 is a schematic diagram of another first signal;

Fig. 18 is a schematic structural diagram of a communication device according to an embodiment of the present application;

Fig. 19 is a schematic structural diagram of another communication device according to an embodiment of the present application;

Fig. 20 is a schematic structural diagram of a network device according to an embodiment of the present application;

fig. 21 is a schematic structural diagram of a terminal device according to an embodiment of the present application.

Detailed Description

As shown in fig. 1, fig. 1 is a schematic structural diagram of a communication system according to an embodiment of the present application. The communication system may include a network device and a terminal device. Wherein:

A network device is an apparatus deployed in a radio access network to provide wireless communication functionality for terminal devices. The network devices may include various forms of macro base stations, micro base stations (also referred to as small stations), relay stations, access points, and the like. In systems employing different radio access technologies, the names of network devices may vary, such as base transceiver stations (base transceiver station, BTSs) in the global system for mobile communications (global system for mobile communication, GSM) or code division multiple access (code division multiple access, CDMA) networks, node bs (NodeB, NB) in wideband code division multiple access (wideband code division multiple access, WCDMA), evolved Node bs (enbs) in long term evolution (long term evolution, LTE). The network device may also be a wireless controller in the context of a cloud wireless access network (cloud radio access network, CRAN). The network device may also be a base station device in a fifth generation mobile communication system (the fifth generation, 5G) network or in next generation wireless communication, or a network device in a future evolved public land mobile network (public land mobile network, PLMN) network. The network device may also be a wearable device or an in-vehicle device. The network device may also transmit a receiving node (transmission and reception point, TRP).

The terminal device may include various handheld devices, vehicle mounted devices, wearable devices, computing devices, or other processing devices connected to a wireless modem with wireless communication capabilities. The terminal device may be a Mobile Station (MS), a subscriber unit (subscriber unit), a cellular phone (cellular phone), a smart phone (smart phone), a wireless data card, a Personal Digital Assistant (PDA) computer, a tablet, a wireless modem (modem), a handheld device (handset), a laptop (labop computer), a machine type communication (MACHINE TYPE communication, MTC) terminal, etc.

The communication system may be applied to a long term evolution (long term evolution, LTE) system, a universal mobile telecommunications system (universal mobile telecommunications system, UMTS) system, a code division multiple access (code division multiple access, CDMA) system, a wireless local area network (wireless local area network, WLAN) or a fifth generation mobile telecommunications system (the fifth generation, 5G) or a next generation wireless telecommunications system, etc.

Peak-to-average power ratio (peak to average power ratio, PAPR), also known as peak-to-average ratio. The wireless signal is a sine wave with continuously changing amplitude in the time domain, the amplitude is not constant, and the amplitude peak value of the signal in one period is different from the amplitude peak value in other periods, so that the average power and the peak power of each period are different. Over a longer period of time, the peak power is the maximum transient power that occurs with some probability, typically the probability is taken to be 0.01% (i.e., 10 ^-4). The ratio of the peak power at this probability to the total average power of the system is the peak-to-average ratio. As shown in fig. 2, fig. 2 is a schematic diagram of peak power and average power. Two lines are included in fig. 2, the first line being peak power, the second line being average power, the ratio of peak power to average power being peak-to-average power.

The system peak-to-average ratio is affected by (1) the peak-to-average ratio of a baseband signal, e.g., 1024-QAM modulated baseband signal, the peak-to-average ratio is large, quadrature PHASE SHIFT KEYING (QPSK) modulated, binary PHASE SHIFT KEYING (BPSK) modulated baseband signal, and the peak-to-average ratio is 1. Among them, QPSK and BPSK can be understood as a signal whose amplitude is constant, changing only the phase. (2) The peak-to-average ratio introduced by the multi-carrier power superposition is, for example, 10 log n for orthogonal frequency division multiplexing (orthogonal frequency division multiplexing, OFDM). As shown in fig. 3, fig. 3 is a schematic diagram of an OFDM amplitude. The ordinate is the OFDM amplitude, the abscissa is the subcarrier index, and the ratio of the peak power to the average power of OFDM is large.

1. Phase noise (PHN):

Since high frequencies (frequency bands above 6G, mainly including 28G, 39G, 60G, 73G, etc.) have abundant frequency band resources, they are becoming industry-accepted for solving the increasing communication demands, and are becoming a hotspot for research and development. The high-frequency communication system has the remarkable characteristics that the high-frequency communication system comprises a large bandwidth and a high-integration antenna array to realize high throughput, and also comprises serious middle radio frequency distortion problems such as phase noise and center frequency offset (carrier frequency offset, CFO), and in addition, the Doppler frequency shift of high frequency is larger, and the phase error is introduced into the high-frequency communication system, so that the performance of the high-frequency communication system is reduced or even the high-frequency communication system cannot work.

Taking phase noise as an example, as the frequency band increases, the higher the power spectral density of the phase noise, the greater the impact on the received signal. For example, as shown in fig. 4, fig. 4 is a schematic diagram of the effect of phase noise on a received signal. The left diagram of fig. 4 shows the phase noise compensated received signal, and the right diagram of fig. 4 shows the uncompensated received signal. When the frequency band is high, the demodulation performance is poor due to the degradation of phase noise, so that the phase tracking reference signal (PHASE TRACKING REFERENCE SIGNAL, PTRS) is introduced for two waveforms (cyclic prefix orthogonal frequency division multiplexing (CP-OFDM) and DFT-s-OFDM) in the existing New Radio (NR) protocol, so as to compensate the influence of phase noise and improve the demodulation performance under the phase noise condition.

The effect of phase noise can be expressed as: Where x (n) is a transmission signal and y (n) is a reception signal. n=0, 1..n-1, N is the time domain sampling point. In brief, a random phase value is generated at each sampling point n. An important non-ideal effect associated with high frequency transmission is phase noise. In the time domain, phase noise is manifested by a phase offset to the standard constellation point. In the existing protocol, the phase noise is estimated and compensated by introducing a phase tracking reference signal.

2. Orthogonal frequency division multiplexing (discrete Fourier Transform spreading OFDM, DFT-s-OFDM) of discrete fourier transform spread:

DFT-s-OFDM is a signal generation scheme for the uplink of LTE. Since DFT-s-OFDM has an additional discrete fourier transform (discrete fourier transform, DFT) process prior to the conventional OFDM process, DFT-s-OFDM may also be referred to as a linear precoding OFDM technique.

As shown in fig. 5, fig. 5 is a schematic process flow diagram of a DFT-s-OFDM technique. The transmitting end sequentially performs serial-to-parallel (serial-to-parallel) conversion, N-point discrete Fourier transform (discrete Fourier transformation, DFT), subcarrier mapping (subcarrier mapping), M-point inverse discrete Fourier transform (INVERSE DISCRETE Fourier transform, IDFT), parallel-to-serial (paralle-to-serial) conversion, cyclic Prefix (CP) addition and digital-to-analog conversion (digital to analog converter, DAC) processing on the time domain discrete sequences, and then transmits signals through antenna ports and channels (channels). When the receiving end receives signals through the channel and the antenna port, analog-to-digital conversion (analog to digital converter, ADC), cyclic prefix removal, serial-to-parallel (serial-to-parallel) conversion, M-point DFT, subcarrier removal mapping, N-point IDFT and parallel-to-serial (parallel-to-parallel) conversion are sequentially carried out on the signals so as to obtain a time domain discrete sequence.

The nature of DFT-s-OFDM is also single carrier. Physically, the operation of DFT-map-inverse fast fourier transform (INVERSE FAST fourier transform, IFFT) is effectively equivalent to convolving the signal input before DFT with one Sinc waveform. Because the nature is single carrier, the PAPR of DFT-s-OFDM is lower than that of OFDM, so that the power transmission efficiency of the mobile terminal can be improved, the service time of a battery can be prolonged, and the cost of the terminal can be reduced.

3. SC-OQAM/DFT-s-OFDM with FTSS (equivalent two implementations):

SC-OQAM is not an implementation of the third generation partnership project (3rd generation partnership project,3GPP) protocol, whereas DFT-S-OFDM is a protocol-defined implementation. Future protocols may define SC-OQAM or DFT-S-OFDM with FTSS. But essentially both implementations are equivalent and can reduce the PAPR of the DFT-S-OFDM waveform, so both implementations are an alternative waveform technique for future mobile communications (6g+) and high frequency scenarios.

First, SC-OQAM (DFT-S-OFDM with FTSS time domain implementation):

As shown in fig. 6, fig. 6 is a schematic diagram of SC-OQAM signal processing. The transmitting end firstly processes the modulated complex signals to obtain real signals and imaginary signals, then carries out up sampling (up sampling) processing on the real signals, carries out up sampling processing and T/2 time delay processing on the imaginary signals, combines the two paths of signals, and finally carries out pulse shaping (pulse shaping) and down sampling (down sampling) processing on the combined signals. As shown in fig. 7, fig. 7 is a schematic diagram of SC-QAM signal processing. The transmitting end sequentially carries out modulation (up-sampling), pulse shaping and down-sampling processing on the signals.

It can be seen that SC-OQAM differs from SC-QAM in that SC-OQAM separates the real and imaginary parts of the complex modulated signal, and then performs T/2 delay on one of the signals, with the other steps being the same.

As shown in fig. 8, fig. 8 is a schematic diagram of an SC-QAM waveform. The SC-QAM carries complex signals (QAM signals, etc.), and takes a root-raised cosine (RRC) filter as an example, the waveform of the SC-QAM is complex-quadrature. Where the complex quadrature relationship indicates that an SC-QAM waveform carries a complex signal and that there is a quadrature relationship between one waveform and the next carrying waveform (i.e., the waveform is 0 at the sample of the next carrying waveform).

As also shown in fig. 9, fig. 9 is a schematic diagram of an SC-OQAM waveform. When the SC-QAM modulation is changed to the SC-OQAM modulation, the complex orthogonal relationship is changed to a partial orthogonal relationship of real and imaginary parts, which in turn means partial interference. Where a partially orthogonal relationship means that one SC-OQAM waveform carries a signal with separated real and imaginary parts, the interference is orthogonal with respect to the signal because of the non-orthogonal relationship between one waveform and the next signal-carrying waveform (i.e., the waveform is not 0 at the sample of the next waveform-carrying signal), but because the information carried by the next signal-carrying waveform is orthogonal. This waveform is in an orthogonal relationship with the waveforms of the next two carrying signals. And thus are orthogonal for the next two signals.

Because of the partial orthogonal relationship, the receiving end discards the imaginary part when receiving the real signal and discards the real part when receiving the imaginary signal. So that the message can be correctly replied. The real-imaginary part orthogonality has the advantage that the peaks of the real part waveform can be overlapped with the non-peaks of the imaginary part signal, and the PAPR can be effectively reduced by the method of staggering the peaks.

DFT-s-OFDM with FTSS (frequency domain implementation of SC-OQAM):

As shown in FIG. 10, FIG. 10 is a schematic diagram of DFT-S-OFDM with FTSS signal processing. The transmitting end splits QAM constellation points used in DFT-S-OFDM systems into real and imaginary signals (it is also possible to directly define the input as PAM signals instead of QAM signals)). Then double up-sampling is performed, i.e., the real signal becomes [ X,0, ], the imaginary signal becomes [ jY,0, jy,0, ], then the imaginary signal is subjected to a time delay, the imaginary signal becomes [0, jy, ], and then after combining becomes [ X, jY, X, jY, X, jY, ], the total length of the combined signal becomes 2 times that of the original complex modulated signal. The phase rotated/real-imaginary separated symbol is then subjected to a 2N-point DFT transform. It should be noted that the above signal processing method is only a special case, and may be split into two complex signals, as long as the phase difference between one signal and the other signal satisfies And (3) obtaining the product.

The 2N point post DFT signal is then frequency domain shaped (frequency domain truncate spectrum shaping, FTSS). The specific mode is that for the downlink transmission direction, the terminal equipment receives transmission resources configured or indicated by the network equipment and FTSS parameters, wherein FTSS parameters comprise one or more of resource bandwidth and center frequency point, modulation mode, original signal bandwidth, filter type and filter parameters, and the resource bandwidth is the bandwidth of the signal received by the terminal equipment and the center frequency point. Frequency filtering is performed according to the indicated signal bandwidth and the filter parameters.

As shown in FIG. 11, FIG. 11 is a schematic diagram of the filtering of DFT-S-OFDM with FTSS. First, because of the real-imaginary part separated QAM constellation modulation, the length of the signal is twice that of the conventional QAM constellation modulation, and the length (size) of the DFT is also twice that of the QAM constellation modulation. The signal after DFT has a characteristic that the spectrum has conjugate symmetry, s n=s ^* N-N, i.e. a and flip (Filp) (a) are shown in the figure, a represents the conjugate. Thus, the data after DFT is redundant in practice. Thus, a truncated frequency domain filtering can be performed on the redundant signal. Where truncation refers to the bandwidth of the filter being less than the bandwidth after DFT. For example, the bandwidth after DFT is 100RB, and the frequency domain filter can be designed to be 60RB long. The filtering process is that the frequency domain filter multiplies the signal directly after the DFT. Since the signal itself is redundant, filtering after truncation does not result in performance loss. Finally, after IFFT transformation, CP is added and transmitted.

In summary, the essence of either SC-OQAM or DFT-S-OFDM with FTSS is to separate the real and imaginary parts and then pass through a shaping filter. This implementation has a lower PAPR than the traditional complex implementation, mainly because the overlapping of the signals after the real and imaginary parts are separated is staggered.

In a 5G high frequency scenario, the DFT-S-OFDM waveform of the existing protocol introduces PTRS to account for estimating and compensating phase noise. As shown in fig. 12, fig. 12 is a schematic diagram of a PTRS pattern of DFT-s-OFDM. Each bin in the figure represents a sample point, i.e. a QAM symbol, pi/2 BPSK symbol or QPSK symbol (the explanation applies to all similar figures, unless otherwise specified below), and the parameters of the pattern include a number of PTRS groups (number of PT-RS groups) N and a number of intra-group sampling points (number of SAMPLES PER PT-RS groups) M, i.e. the total number of PTRS is N x M, the specific mapping positions being related to both parameters and the scheduling bandwidth.

When the number of samples m=2 in the group, the scheduling bandwidth is uniformly divided into N segments or N intervals, and one PTRS group is mapped in the middle of each segment, as shown in the first row and the third row in fig. 12. When the number of sampling points m=4 in the group, the scheduling bandwidth is uniformly divided into N segments or N intervals, each segment or each interval will map a PTRS group, where the PTRS group of the first segment is mapped at the head of the first segment, the PTRS group of the nth segment is mapped at the tail of the nth segment, and the PTRS groups of other segments (intervals) are mapped in the middle, as shown in the second row (only two segments at this time, and therefore, there are no PTRS groups mapped in the middle of the segments), the fourth row, and the fifth row of fig. 12.

The two parameters are implicitly determined by the current scheduling bandwidth based on a pre-configured mapping relationship (corresponding relationship between the scheduling bandwidth and the parameters, as shown in table 1, NRB0 to NRB4 are pre-configured values) in the transmission process. For the same terminal device and the same network device (same frequency point and subcarrier spacing), the scheduling bandwidths corresponding to the 5 groups of parameters in fig. 12 show a monotonically increasing trend.

TABLE 1

Scheduling bandwidth	PTRS group number N	Intra-group sampling point number M
			NRB0<=NRB<NRB1	2	2
NRB1<=NRB<NRB2	2	4
			NRB2<=NRB<NRB3	4	2
NRB3<=NRB<NRB4	4	4
			NRB4<=NRB	8	4

When the modulation mode of the transmission signal is changed from the conventional QAM constellation point to the OQAM modulation with low PAPR, the influence of the phase noise cannot be estimated by the separation of the real part and the imaginary part, for the following reasons:

assuming no phase noise, the received signal can be expressed as:

Where x denotes the received signal, P is the real part signal, and ISI denotes the intersymbol interference (inter-symbol interference). I.e. for a transmitted real signal, the interference is reflected in the imaginary part, and the imaginary part is therefore discarded, i.e. the real signal P can be demodulated. One summation term is due to the interference of one waveform that may have multiple order components. As shown in fig. 13, fig. 13 is a schematic diagram of a filter with waveform interference. The interference of the waveform includes a first order interference component and a second order interference component. I.e. not just the nearest real signal, but also the next X real signals. This length is related to the roll-off design of the waveform, where the design of the waveform is not constrained.

But when there is a phase noise influence, the received signal can be expressed as:

the phase noise causes the signal of the pure imaginary part to leak to the real part, and the euler expansion of the above formula can be known:

Thus, the real part becomes Since the interference term and the phase noise are unknown, interference cannot be separated from the signal, resulting in performance loss. As shown in fig. 14, fig. 14 is a schematic diagram of a performance comparison. The left plot of fig. 14 is the SC-OQAM noisy constellation points and the right plot of fig. 14 is the SC-OQAM noisy constellation points.

In order to solve the technical problems, the embodiment of the application provides the following solutions.

As shown in fig. 15, fig. 15 is a flow chart of a communication method according to an embodiment of the present application. The method mainly comprises the following steps:

S1501, a network device generates a first signal, where the first signal includes a first path signal and a second path signal, the first path signal includes X first data signals, and the first data signals are The second path signal comprises Y second data signals and M first phase noise tracking pilot signals PTRS, wherein the second data signals areThe first PTRS isThe θ ₁ belongs to [0,2π), the θ ₂ belongs to [0,2π),The M first PTRS are used for processing phase noise, the first path of signals and the second path of signals are continuously interwoven, X, Y, M and N are integers which are larger than or equal to 1, and a, b and c are real numbers.

The first signal may be an SC-OQAM signal or a DFT-S-OFDM with FTSS signal. The first signal includes a first signal and a second signal, and the first signal or the second signal may include the following forms:

In one implementation, the first path signal includes X first data signals that are real signals, e.g., when θ ₁ =0. The second data signals include Y second data signals which are imaginary signals, e.g. when When Y second data signals are imaginary signals, the first data signals and the second data signals are orthogonal. In the case that the first data signal is a real signal and the second data signal is an imaginary signal, M first PTRSs included in the first path signal are real pilot signals, and the first PTRSs are orthogonal to the second data signal.

In another implementation, the first data signals included in the first path signal are imaginary signals, e.g. whenThe X first data signals are imaginary signals. The second data signals include Y second data signals that are real signals, for example, when θ ₂ =0, the first data signals and the second data signals are orthogonal. In the case where the first data signal is an imaginary signal and the second data signal is a real signal, M first PTRSs included in the second path signal are imaginary pilot signals, the first PTRSs being orthogonal to the second data signal.

In another implementation manner, the X first data signals included in the first path of signals may be complex signals, the Y first data signals included in the second path of signals may also be complex signals, and the M first PTRS included in the second path of signals may also be complex pilot signals. Wherein the phase difference between the first data signal and the second data signal isThe phase difference between the first PTRS and the second data signal is

The first signal may be continuously interleaved between the first signal and the second signal. The continuous interleaving arrangement may be represented as a1 st position in the first signal setting a1 st data in the first way signal, a 2 nd position in the first signal setting a1 st data in the second way signal, a 3 rd position in the first signal setting a 2 nd data in the first way signal, a 4 th position in the first signal setting a 2 nd data in the second way signal, a 5th position in the first signal setting a 3 rd data in the first way signal. The following description will be made with the first data signal as a real signal, the second data signal as an imaginary signal, and the first PTRS as a real pilot signal.

For example, the first signal is [1,1j,1, -j, -1, j ], and the first signal is numbered as [1,2,3,4,5, 6. The [1,3,5, 7. ] signals are referred to as I-way, the carried data signals are I-way (real) signals, and the I-way signals are [1, -1]. The [2,4,6, 8. ] signals are referred to as Q-way, the carried data signals are Q-way (imaginary) signals, and the Q-way signals are [1j, -j, j ]. The Q-way signal also includes a first PTRS, which is a real pilot signal. For example, the first PTRS is 1, and the first PTRS is set at the 2 nd position in the Q-way signal, that is, the 4 th position of the first signal, and the imaginary signal (1 j) at the 4 th position in the first signal is replaced with 1, and the first signal is adjusted to [1,1j,1, -j, -1, j ].

In the first signal, the sign polarity of the first PTRS is the same as the sign polarity of the adjacent data or the data with even interval, and the sign polarity of the first PTRS is opposite to the sign polarity of the data with odd interval. The same sign polarity means belonging to either an imaginary signal at the same time or a real signal at the same time, and the opposite sign polarity means not belonging to either a real signal at the same time or an imaginary signal at the same time. For example, in the first signal [1,1j,1, -j, -1, j ], the first PTRS is 1, which is a real signal, and adjacent data or data with even intervals are [1, -1], which are real signals, respectively, and the sign polarity of the first PTRS is the same. The data with odd intervals are respectively [1j, -j, j ], are all imaginary signals, and have opposite sign polarity with the first PTRS.

Optionally, the positive and negative phases of the first PTRS are determined according to the positive and negative phases of the interference of the data carried by the first signal to the first PTRS. Further, the positive and negative phases of the first PTRS are the same as the positive and negative phases of the interference of the data carried by the first signal to the first PTRS. For example, if the sum of interference of the data carried by the first signal to the first PTRS is 0.2, the first PTRS may select a positive phase. As another example, if the first PTRS is 1, the sum of the interference of the first PTRS and the data carried by the first signal to the first PTRS is 1.2, so that the energy of the first PTRS is maximum. Alternatively, since it is complex to calculate the interference of all the data carried by the first signal on the first PTRS, the positive and negative phases of the first PTRS may be determined according to the positive and negative phases of the data adjacent to the first PTRS. The positive and negative phases of the first PTRS are the same as the positive and negative phases of adjacent data.

Optionally, the first path signal further includes M second PTRSs, one of the second PTRSs corresponds to one of the first PTRSs, and the second PTRS isThe M second PTRSs are used for carrying data, the M second PTRSs are not used for processing phase noise, and d is a real number. I.e. the first PTRS is a real pilot signal and the second PTRS is an imaginary pilot signal, or the first PTRS is an imaginary pilot signal and the second PTRS is a real pilot signal. The first PTRS is orthogonal to the second PTRS, or the phase difference between the first PTRS and the second PTRS is

Optionally, the second PTRS is adjacent to the first PTRS. So as to adjust the positive and negative phases of the second PTRS in the first path signal so as to more closely match the effect on the first PTRS in the second path signal. In addition, the positive and negative phases of the second PTRS are the same as the positive and negative phases of the first PTRS, so that the positive and negative phases of the interference of the second PTRS to the first PTRS are the same as the positive and negative phases of the first PTRS, and the energy of the first PTRS is maximum.

For example, as shown in fig. 16, fig. 16 is a schematic diagram of a first signal. The first signal includes a first path signal and a second path signal, the first path signal includes 4 real signals and 1 imaginary pilot signal I, the 4 real signals are respectively located at a position #1, a position #5, a position #7 and a position #9 in the first signal, and the imaginary pilot signal I is located at a position #3 in the first signal. The second path signal includes 3 imaginary signals and 1 real pilot signal Q, the 3 imaginary signals being located at position #2, position #6 and position #8 in the first signal, respectively, and the 1 real pilot signal Q being located at position #4 in the first signal. The first path of signals and the second path of signals are arranged in a continuous interleaving mode. An imaginary pilot signal I corresponds to a real pilot signal Q, the imaginary pilot signal I being adjacent to the real pilot signal Q, the imaginary pilot signal I being used for carrying data, the real pilot signal Q being used for processing phase noise. Fig. 16 shows PTRS patterns of only one set of signals, as such for other sets of PTRS patterns, and will not be described again here.

It should be noted that if the first PTRS exists in the second path signal and the second PTRS does not exist in the first path signal, the second PTRS may be considered as a data signal. The positive and negative phases of the data signal are the same as those of other data in the first path signal, which interfere with the first PTRS. The data signal may be a data signal at an index position preceding the first PTRS in the first signal or a data signal at a first path signal at an index position following the first PTRS in the first signal.

Optionally, the M first PTRSs are disposed at equal intervals in the second signal path. That is, if the second path signal includes a plurality of first PTRSs, the plurality of first PTRSs are equally spaced in the second path signal. Alternatively, an odd number of data may be spaced between two consecutive first PTRS in the second signal. Wherein the second PTRS is adjacent to the first PTRS, and the positive and negative phases of interference of the second PTRS to the first PTRS are the same as the positive and negative phases of interference of data adjacent to the second PTRS.

For example, as shown in fig. 17, fig. 17 is a schematic diagram of another first signal. The first signal comprises a first path of signals and a second path of signals, the first path of signals comprises 2 real signals and 2 imaginary pilot signals I, the 2 real signals are respectively positioned at a position #3 and a position #5 in the first signal, and the 2 imaginary pilot signals I are respectively positioned at a position #1 and a position #7 in the first signal. The second path signal includes 1 imaginary signal at position #4 in the first signal and 2 real pilot signals Q at positions #2 and #6 in the first signal, respectively. Wherein, an imaginary pilot signal I is adjacent to a real pilot signal Q, 2 imaginary pilot signals I are not used for processing phase noise by the receiving end, and 2 real pilot signals Q are used for processing phase noise by the receiving end.

The interference effect of the data on position #1 on position #2, position #4 and position #6 is 0.6, -0.16 and 0.05, respectively, due to the interference characteristics of the filter. In general, the effect of the filter is positive, negative, positive, negative. The effect of the odd order is positive and the effect of the even order is negative. Therefore, in order to make the uniformity of the influence of the data on the 2 real pilot signals Q, for example, the uniformity of the influence of the data on the position #1 on the real pilot signal Q on the position #2 and the real pilot signal Q on the position #6 (both are positive phases), 2 real pilot signals Q in the second path signal are arranged at equally spaced positions in the second path signal with one data therebetween. In addition, one imaginary pilot signal I is adjacent to one real pilot signal Q, so as to adjust the positive and negative phases of 2 imaginary pilot signals I in the first path signal, so that the influence on 2 real pilot signals Q in the second path signal is more matched. Fig. 17 shows PTRS patterns of only one set of signals, as such for other sets of PTRS patterns, and will not be described again here.

S1502, the network device sends a first signal to the terminal device.

Alternatively, the network device may send a predefined PTRS pattern to the terminal device, which PTRS pattern is used to determine PTRS parameters. The PTRS parameters may include the number of PTRS groups N and the number of intra-group sampling points M, among others.

And S1503, the terminal equipment processes the phase noise based on the M first PTRS.

Specifically, the terminal device may determine a current scheduling bandwidth, determine a PTRS parameter corresponding to the PTRS pattern according to the current scheduling bandwidth, determine a mapping position of the first PTRS in the first signal based on the PTRS parameter, obtain the first PTRS at the mapping position in the first signal, and process the phase noise through the first PTRS.

In the embodiment of the application, the phase angle between the first path of signal and the second path of signal is satisfied by the continuous interweaving arrangement of the first path of signal and the second path of signalAnd a first PTRS for processing phase noise is set in the second signal. For example, the first path of signal is a real signal, and a real pilot signal is set at a position where an imaginary signal is originally set in the second path of signal, so that interference of data carried by the first signal on the first PTRS is in the same direction as the first PTRS, and signal energy of the first PTRS is maximized. Thus, the first PTRS is utilized to process the phase noise, and the accuracy of the phase noise processing is improved.

It should be understood that, in the foregoing embodiments of the methods and operations implemented by the terminal device, the methods and operations implemented by the network device may also be implemented by a component (e.g., a chip or a circuit) that may be used in the terminal device, or the methods and operations implemented by the network device may also be implemented by a component (e.g., a chip or a circuit) that may be used in the network device.

The embodiment of the application can divide the functional modules of the terminal equipment or the network equipment according to the method example, for example, each functional module can be divided corresponding to each function, and two or more functions can be integrated in one processing module. The integrated modules described above may be implemented either in hardware or in software functional modules. It should be noted that, in the embodiment of the present application, the division of the modules is schematic, which is merely a logic function division, and other division manners may be implemented in actual implementation. The following description will be given by taking an example of dividing each function module into corresponding functions.

The method provided by the embodiment of the present application is described in detail above with reference to fig. 15. The following describes in detail a communication device provided in an embodiment of the present application with reference to fig. 18 to 19. It should be understood that the descriptions of the apparatus embodiments and the descriptions of the method embodiments correspond to each other, and thus, descriptions of details not described may be referred to the above method embodiments, which are not repeated herein for brevity.

Referring to fig. 18, fig. 18 is a schematic structural diagram of a communication device according to an embodiment of the application. The communication device may include a processing module 1801 and a transmitting module 1802.

The communication apparatus may implement steps or procedures performed by the network device in the above method embodiments, for example, may be the network device, or a chip or a circuit configured in the network device. The sending module 1802 is configured to perform a transceiver-related operation on the network device side in the above method embodiment, and the processing module 1801 is configured to perform a processing-related operation on the network device in the above method embodiment.

A processing module 1801, configured to generate a first signal, where the first signal includes a first path signal and a second path signal, the first path signal includes X first data signals, and the first data signals areThe second path signal comprises Y second data signals and M first phase noise tracking pilot signals PTRS, wherein the second data signals areThe first PTRS isThe θ ₁ belongs to [0,2π), the θ ₂ belongs to [0,2π),The M first PTRS are used for processing phase noise, the first path of signals and the second path of signals are continuously interleaved, X, Y, M and N are integers which are more than or equal to 1, and a, b and c are real numbers;

A transmitting module 1802, configured to transmit a first signal to a terminal device.

Optionally, the positive and negative phases of the first PTRS are determined according to the positive and negative phases of the interference of the data carried by the first signal to the first PTRS.

Optionally, the positive and negative phases of the first PTRS are the same as the positive and negative phases of the interference of the data carried by the first signal to the first PTRS.

Optionally, the first path signal further includes M second PTRSs, one of the second PTRSs corresponds to one of the first PTRSs, and the second PTRS isThe M second PTRSs are used for carrying data, and d is a real number.

Optionally, the positive and negative phases of the second PTRS are the same as the positive and negative phases of the first PTRS.

Optionally, the second PTRS is adjacent to the first PTRS.

Optionally, the M first PTRSs are disposed at equal intervals in the second signal path.

Optionally, the sending module 1802 is further configured to send a predefined PTRS pattern to the terminal device, where the PTRS pattern is used to determine a PTRS parameter.

It should be noted that, the implementation of each module may also correspond to the corresponding description of the method embodiment shown in fig. 15, and perform the method and the function performed by the network device in the foregoing embodiment.

Referring to fig. 19, fig. 19 is a schematic structural diagram of another communication device according to an embodiment of the present application. The communication device may include a receiving module 1901 and a processing module 1902.

The communication apparatus may implement steps or procedures performed by the terminal device in the above method embodiments, for example, may be the terminal device, or a chip or a circuit configured in the terminal device. The receiving module 1901 is configured to perform a transceiver-related operation on the terminal device side in the above method embodiment, and the processing module 1902 is configured to perform a processing-related operation on the terminal device in the above method embodiment.

A receiving module 1901, configured to receive a first signal sent by a network device, where the first signal includes a first path signal and a second path signal, the first path signal includes X first data signals, and the first data signals areThe second path signal comprises Y second data signals and M first phase noise tracking pilot signals PTRS, wherein the second data signals areThe first PTRS isThe θ ₁ belongs to [0,2π), the θ ₂ belongs to [0,2π),The M first PTRS are used for processing phase noise, the first path of signals and the second path of signals are continuously interleaved, X, Y, M and N are integers which are more than or equal to 1, and a, b and c are real numbers;

a processing module 1902, configured to process phase noise based on the M first PTRSs.

Optionally, the second PTRS is adjacent to the first PTRS.

Optionally, the receiving module 1901 is further configured to receive a predefined PTRS pattern sent by the network device, where the PTRS pattern is used to determine a PTRS parameter.

It should be noted that, the implementation of each module may also correspond to the corresponding description of the method embodiment shown in fig. 15, and perform the method and the function performed by the terminal device in the foregoing embodiment.

Fig. 20 is a schematic structural diagram of a network device according to an embodiment of the present application. The network device may be applied to the system shown in fig. 1, to perform the functions of the network device in the above method embodiment, or to implement the steps or flows performed by the network device in the above method embodiment.

As shown in fig. 20, the network device includes a processor 2001 and a transceiver 2002. Optionally, the network device further comprises a memory 2003. Wherein the processor 2001, the transceiver 2002 and the memory 2003 can communicate with each other via an internal connection path for transferring control and/or data signals, the memory 2003 is used for storing a computer program, the processor 2001 is used for calling and running the computer program from the memory 2003 for controlling the transceiver 2002 to transmit and receive signals. Optionally, the network device may further include an antenna for sending uplink data or uplink control signaling output by the transceiver 2002 via a wireless signal.

The processor 2001 may be combined with the memory 2003 into a single processing device, and the processor 2001 is configured to execute program codes stored in the memory 2003 to realize the functions. In particular, the memory 2003 may also be integrated into the processor 2001 or independent of the processor 2001. The processor 2001 may correspond to the processing module in fig. 18.

The transceiver 2002 may correspond to the transmission module shown in fig. 18, and may be referred to as a transceiver unit or a transceiver module. The transceiver 2002 may include a receiver (or receiver, receiving circuitry) and a transmitter (or transmitter, transmitting circuitry). Wherein the receiver is for receiving signals and the transmitter is for transmitting signals.

It should be understood that the network device shown in fig. 20 is capable of implementing the various processes involving the network device in the method embodiment shown in fig. 15. The operations and/or functions of the respective modules in the network device are respectively for implementing the corresponding flows in the above-mentioned method embodiments. Reference is specifically made to the description of the above method embodiments, and detailed descriptions are omitted here as appropriate to avoid redundancy.

The above-described processor 2001 may be used to perform the actions described in the previous method embodiments as being performed internally by the network device, while the transceiver 2002 may be used to perform the actions described in the previous method embodiments as being transmitted to or received from the terminal device by the network device. Please refer to the description of the foregoing method embodiments, and details are not repeated herein.

The processor 2001 may be a central processing unit, a general purpose processor, a digital signal processor, an application specific integrated circuit, a field programmable gate array or other programmable logic device, a transistor logic device, a hardware component, or any combination thereof. Which may implement or perform the various exemplary logic blocks, modules and circuits described in connection with this disclosure. Processor 2001 may also be a combination of computing functions, e.g., comprising one or more microprocessor combinations, a combination of digital signal processors and microprocessors, and the like. The communication bus 2004 may be a peripheral component interconnect standard PCI bus or an extended industry standard architecture EISA bus or the like. The buses may be classified as address buses, data buses, control buses, etc. For ease of illustration, only one thick line is shown in fig. 20, but not only one bus or one type of bus. The communication bus 2004 is used to enable connected communications between these components. The transceiver 2002 is used for signaling or data communication with other node devices in the embodiment of the present application. The memory 2003 may include volatile memory such as nonvolatile dynamic random access memory (nonvolatile random access memory, NVRAM), phase change random access memory (PHASE CHANGE RAM, PRAM), magnetoresistive random access memory (magetoresistive RAM, MRAM), etc., and may also include nonvolatile memory such as at least one magnetic disk storage device, electrically Erasable Programmable Read Only Memory (EEPROM), flash memory device such as NOR flash memory (NOR flash memory) or NAND flash memory (NAND FLASH memory), semiconductor device such as solid state disk (solid state drive STATE DISK, SSD), etc. The memory 2003 may also optionally be at least one storage device located remotely from the aforementioned processor 2001. Optionally, a set of computer program code or configuration information may also be stored in the memory 2003. Optionally, the processor 2001 may also execute a program stored in the memory 2003. The processor may cooperate with the memory and the transceiver to perform any of the methods and functions of the network device in the embodiments of the application described above.

Fig. 21 is a schematic structural diagram of a terminal device according to an embodiment of the present application. The terminal device may be applied to the system shown in fig. 1, to perform the functions of the terminal device in the above method embodiment, or to implement the steps or flows performed by the terminal device in the above method embodiment.

As shown in fig. 21, the terminal device includes a processor 2101 and a transceiver 2102. Optionally, the terminal device further comprises a memory 2103. Wherein the processor 2101, the transceiver 2102 and the memory 2103 may communicate with each other via an internal connection path for transferring control and/or data signals, the memory 2103 is used for storing a computer program, and the processor 2101 is used for calling and running the computer program from the memory 2103 for controlling the transceiver 2102 to send and receive signals. Optionally, the terminal device may further include an antenna, for sending the uplink data or the uplink control signaling output by the transceiver 2102 through a wireless signal.

The processor 2101 and the memory 2103 may be combined into a single processing device, and the processor 2101 is configured to execute the program code stored in the memory 2103 to implement the functions described above. In particular implementations, the memory 2103 may also be integrated into the processor 2101 or separate from the processor 2101. The processor 2101 may correspond to the processing module in fig. 19.

The transceiver 2102 may correspond to the receiving module in fig. 19, and may also be referred to as a transceiver unit or a transceiver module. The transceiver 2102 may include a receiver (or receiver, receiving circuitry) and a transmitter (or transmitter, transmitting circuitry). Wherein the receiver is for receiving signals and the transmitter is for transmitting signals.

It should be understood that the terminal device shown in fig. 21 is capable of implementing the respective procedures involving the terminal device in the method embodiment shown in fig. 15. The operations and/or functions of the respective modules in the terminal device are respectively for implementing the corresponding flows in the above method embodiments. Reference is specifically made to the description of the above method embodiments, and detailed descriptions are omitted here as appropriate to avoid redundancy.

The processor 2101 described above may be used to perform the actions described in the method embodiments as being performed internally by the terminal device, while the transceiver 2102 may be used to perform the actions described in the method embodiments as being performed by the terminal device as being transmitted to or received from the network device. Please refer to the description of the foregoing method embodiments, and details are not repeated herein.

Among them, the processor 2101 may be various types of processors mentioned above. The communication bus 2104 may be a peripheral component interconnect standard PCI bus or an extended industry standard architecture EISA bus or the like. The buses may be classified as address buses, data buses, control buses, etc. For ease of illustration, only one thick line is shown in fig. 21, but not only one bus or one type of bus. The communication bus 2104 is used to enable connected communications between these components. The transceiver 2102 of the device in the embodiment of the present application is used for signaling or data communication with other devices. The memory 2103 may be the various types of memory mentioned previously. The memory 2103 may also optionally be at least one storage device located remotely from the aforementioned processor 2101. A set of computer program code or configuration information is stored in the memory 2103, and the processor 2101 executes the programs in the memory 2103. The processor may cooperate with the memory and the transceiver to perform any of the methods and functions of the terminal device in the embodiments of the application described above.

The embodiment of the application also provides a chip system, which comprises a processor for supporting a terminal device or a network device to realize the functions involved in any of the above embodiments, for example, generating or processing the first signal involved in the above method.

In one possible design, the chip system may further include a memory for computer programs and data necessary for the terminal device or the network device. The chip system can be composed of chips, and can also comprise chips and other discrete devices. The input and output of the chip system correspond to the receiving and sending operations of the terminal device or the network device in the method embodiment respectively.

According to the method provided by the embodiment of the application, the application further provides a computer program product, which comprises a computer program, when the computer program runs on a computer, for causing the computer to execute the method of any one of the embodiments shown in fig. 15.

According to the method provided by the embodiment of the present application, the present application further provides a computer readable medium storing a computer program, where the computer program when executed on a computer causes the computer to perform the method of any one of the embodiments shown in fig. 15.

According to the method provided by the embodiment of the application, the application also provides a communication system which comprises the one or more terminal devices and one or more network devices.

In the above embodiments, it may be implemented in whole or in part by software, hardware, firmware, or any combination thereof. When implemented in software, may be implemented in whole or in part in the form of a computer program product. The computer program product includes one or more computer instructions. When the computer instructions are loaded and executed on a computer, the processes or functions described in accordance with embodiments of the present application are produced in whole or in part. The computer may be a general purpose computer, a special purpose computer, a computer network, or other programmable apparatus. The computer instructions may be stored in a computer-readable storage medium or transmitted from one computer-readable storage medium to another computer-readable storage medium, for example, the computer instructions may be transmitted from one website, computer, server, or data center to another website, computer, server, or data center by a wired (e.g., coaxial cable, fiber optic, digital subscriber line (digital subscriber line, DSL)) or wireless (e.g., infrared, wireless, microwave, etc.). The computer readable storage medium may be any available medium that can be accessed by a computer or a data storage device such as a server, data center, etc. that contains an integration of one or more available media. The usable medium may be a magnetic medium (e.g., a floppy disk, a hard disk, a magnetic tape), an optical medium (e.g., a high-density digital video disc (digital video disc, DVD)), or a semiconductor medium (e.g., a solid-state disk (solid-state drive STATE DISC, SSD)), or the like.

The foregoing is merely illustrative of the present application, and the present application is not limited thereto, and any person skilled in the art will readily recognize that variations or substitutions are within the scope of the present application. Therefore, the protection scope of the present application shall be subject to the protection scope of the claims.

Claims

1. A method of communication, the method comprising:

generating a first signal, wherein the first signal comprises a first path of signals and a second path of signals, the first path of signals comprises X first data signals, and the first data signals are The second path signal comprises Y second data signals and M first phase noise tracking pilot signals PTRS, wherein the second data signals areThe first PTRS isThe θ ₁ belongs to [0,2π), the θ ₂ belongs to [0,2π),The M first PTRS are used for processing phase noise, the first path of signals and the second path of signals are continuously interleaved, X, Y, M and N are integers which are more than or equal to 1, and a, b and c are real numbers;

and sending the first signal to the terminal equipment.

2. The method of claim 1, wherein the positive and negative phases of the first PTRS are determined from positive and negative phases of interference of data carried by the first signal with the first PTRS.

3. The method of claim 2, wherein the positive and negative phases of the first PTRS are the same as the positive and negative phases of interference of data carried by the first signal on the first PTRS.

4. A method according to any of claims 1-3, wherein said first path signal further comprises M second PTRS, one of said second PTRS corresponding to one of said first PTRS, said second PTRS beingThe M second PTRSs are used for carrying data, and d is a real number.

5. The method of claim 4, wherein the positive and negative phases of the second PTRS are the same as the positive and negative phases of the first PTRS.

6. The method of claim 4 or 5, wherein the second PTRS is adjacent to the first PTRS.

7. The method of any of claims 1-6, wherein the M first PTRS are equally spaced in the second signal.

8. The method of any one of claims 1-7, wherein the method further comprises:

and transmitting a predefined PTRS pattern to the terminal equipment, wherein the PTRS pattern is used for determining PTRS parameters.

9. A method of communication, the method comprising:

Receiving a first signal sent by network equipment, wherein the first signal comprises a first path of signal and a second path of signal, the first path of signal comprises X first data signals, and the first data signals are The second path signal comprises Y second data signals and M first phase noise tracking pilot signals PTRS, wherein the second data signals areThe first PTRS isThe θ ₁ belongs to [0,2π), the θ ₂ belongs to [0,2π),The M first PTRS are used for processing phase noise, the first path of signals and the second path of signals are continuously interleaved, X, Y, M and N are integers which are more than or equal to 1, and a, b and c are real numbers;

and processing the phase noise based on the M first PTRS.

10. The method of claim 9, wherein the positive and negative phases of the first PTRS are determined from positive and negative phases of interference of data carried by the first signal with the first PTRS.

11. The method of claim 10, wherein the positive and negative phases of the first PTRS are the same as the positive and negative phases of interference of data carried by the first signal on the first PTRS.

12. The method of any of claims 9-11, wherein the first path signal further comprises M second PTRS, one of the second PTRS corresponding to one of the first PTRS, the second PTRS beingThe M second PTRSs are used for carrying data, and d is a real number.

13. The method of claim 12, wherein the positive and negative phases of the second PTRS are the same as the positive and negative phases of the first PTRS.

14. The method of claim 12 or 13, wherein the second PTRS is adjacent to the first PTRS.

15. The method according to any one of claims 9-14, wherein the M first PTRS are equally spaced in the second signal.

16. The method of any one of claims 9-15, wherein the method further comprises:

and receiving a predefined PTRS pattern sent by the network equipment, wherein the PTRS pattern is used for determining PTRS parameters.

17. A communication device comprising a memory for storing a computer program and a processor that runs the computer program to cause the communication device to perform the method of any one of claims 1-8.

18. A communication device comprising a memory for storing a computer program and a processor that runs the computer program to cause the communication device to perform the method of any of claims 9-16.

19. A computer readable storage medium, characterized in that the computer readable storage medium comprises a computer program which, when run by a processor, causes the method according to any one of claims 1-16 to be implemented.

20. A chip comprising a processor for communicating with an external device or an internal device and a communication interface for implementing the method of any of claims 1-16.