JP2021083061A - Wireless receiver - Google Patents

Abstract

PROBLEM TO BE SOLVED: To perform phase control of diversity synthesis with high accuracy. SOLUTION: A tap processing unit 14A, 14B that performs a weight multiplication process on a received signal obtained based on a radio signal based on a tap coefficient to output a tap output signal and output a received signal vector of the received signal. The adaptive processing unit 15 that outputs the tap coefficient based on the tap output signal and the received signal vector, the synthesis unit 16 that diversifies the tap output signal and outputs the composite signal, and when the composite signal has the maximum power. It has a power detection unit 17 that outputs the amount of phase rotation, a diversity synthesis unit 20 that diversifies the received signal and outputs a combined reception signal, and a demodulation unit 21 that performs demographic processing on the combined reception signal. After rotating the phase of the received signal based on the amount of rotation of the phase, the diversity synthesis unit 20 performs diversity synthesis to obtain a composite reception signal, and the synthesis reception signal is demoted by the demodulation unit 21. [Selection diagram] Fig. 1

Description

The present invention relates to a wireless receiver that receives received waves arriving at a plurality of branches based on a space diversity method.

Regarding microwave radio reception of a microwave radio communication system, a space diversity method using a plurality of antennas is known as a device for obtaining a good reception signal even under fading conditions generated by radio wave propagation. As a wireless communication technology that utilizes the diversity effect, for example, in a wireless receiving device that realizes space diversity by providing a corresponding branch for each received signal received by a plurality of antennas and synthesizing the received signals of each branch. When diversifying the received signal of the branch by weight processing based on the weighting coefficient, a correction matrix is generated so that the eigenvalue matrix obtained from the received signal vector of the received signal to be weighted becomes the unit matrix. The received signal is converted by the correction matrix, the eigenvector corresponding to the maximum eigenvalue of the covariance matrix obtained from the received signal vector of the converted received signal is calculated, and the diversity synthesis is performed using the eigenvector as a weighting coefficient. It is known (Patent Document 1).

International release WO 2013/018716

By the way, due to the demand for higher efficiency of frequency utilization due to the increase in wireless traffic, the demand for high-speed transmission by the high multi-value QAM (Quadrature Amplitude Modulation) method is increasing in digital wireless transmission. On the other hand, when the conventional space diversity method (specifically, for example, the minimum amplitude deviation synthesis method or the in-phase synthesis method) for the purpose of improving the reception performance is applied to the high multi-level QAM method, the phase control error before the diversity synthesis is applied. When demodulating the signal after diversity synthesis, performance may deteriorate due to the influence of. The technique described in Cited Document 1 has a technical idea of reducing the influence of synthesis error by performing waveform equalization before diversity synthesis, and diversity after performing waveform equalization for the received signal of each branch. I try to synthesize. That is, in the technique described in Cited Document 1, waveform equalization is performed using the received signal of each branch before the effect of improving the received C / N ratio (Carrier to Noise ratio) by diversity is obtained. Therefore, the equalization limit is equivalent to reception with a single antenna, and there is a problem that deterioration of equalization performance due to a decrease in the reception C / N ratio cannot be avoided.

Therefore, an object of the present invention is to provide a wireless receiving device capable of performing phase control of diversity synthesis with high accuracy.

In order to solve the above problems, the invention according to claim 1 is provided for each of a plurality of branches corresponding to each of the plurality of antennas, and is a baseband signal obtained based on a radio signal received by the antennas. An A / D converter that performs analog-digital conversion processing on the received signal and outputs a received signal, and a weight multiplication process that is provided for each of the plurality of branches and performs weight multiplication processing on the received signal based on the tap coefficient. A tap processing unit that outputs a tap output signal and a reception signal vector of the reception signal, and an adaptive processing unit that outputs the tap coefficient based on the tap output signal and the reception signal vector of each of the plurality of branches. A synthesis unit that diversifies the tap output signals of each of the plurality of branches and outputs a composite signal, and a power detection unit that outputs a phase rotation amount when the composite signal has the maximum power. Each branch of the above branch has a diversity synthesis unit that diversifies and outputs the combined reception signal, and a demodulation unit that performs demographic processing on the combined reception signal, based on the amount of rotation of the phase. The radio receiving device is characterized in that after rotating the phase of the received signal, the diversity synthesis unit performs diversification synthesis to obtain the combined reception signal, and the combined reception signal is demoted by the demodulation unit.

The invention according to claim 2 is characterized in that, in the wireless receiving device according to claim 1, the modulation method of the wireless signal received by the antenna is four-phase shift keying.

The invention according to claim 3 is characterized in that, in the wireless receiving device according to claim 1 or 2, the number of the branches is two.

According to the invention of claim 1, since the waveform is equalized with the signal obtained by the performance improving effect of the received C / N ratio by the diversity synthesis, the waveform is equalized in the environment where the received C / N ratio is lowered. The equalization performance can be significantly improved, highly accurate diversity synthesis can be performed, and it is possible to prevent deterioration of high multi-value demodulation in the signal after synthesis. According to the invention of claim 1, an adaptive equalization process is incorporated in the power detection for phase adjustment of diversity synthesis, and the power is detected after synthesizing the equalized signal. Therefore, it is possible to perform highly accurate phase control by eliminating the influence of interference due to reflected waves and delay error between antennas. According to the invention of claim 1, since the purpose is to detect power, high-precision equalization is not required, and an equalization algorithm that operates stably even when the reception C / N ratio is low is adopted. be able to.

According to the second aspect of the present invention, it is possible to achieve the above effect in wireless communication performed by using the four-phase shift keying method.

According to the third aspect of the invention, it is possible to achieve the above-mentioned effect in diversity synthesis in which the number of branches is two.

It is a functional block diagram which shows the schematic structure of the wireless receiver device which concerns on embodiment of this invention. It is a functional block diagram which shows the schematic structure of the circuit for verifying the correlation detection characteristic of the wireless receiver shown in FIG. It is a graph which shows the correlation detection characteristic of the wireless receiver shown in FIG. 1 by the circuit shown in FIG.

Hereinafter, the present invention will be described based on the illustrated embodiment. In the following, the characteristic configuration of the present invention will be described, and the description of the same mechanism as the conventional one when communicating by the space diversity method will be omitted.

FIG. 1 is a functional block diagram showing a schematic configuration of a wireless receiver 1 according to an embodiment of the present invention. This wireless receiving device 1 is for performing wireless communication (particularly microwave wireless communication) between a fixed station on the transmitting side in which a single antenna is installed and a fixed station on the receiving side in which a plurality of antennas are installed. In addition, it is a mechanism provided in the fixed station on the receiving side.

The radio receiving device 1 according to this embodiment is provided for each of two branches (here, the first branch and the second branch) corresponding to each of the two antennas 11A and 11B, and is received by the antennas 11A and 11B. A / D converters 13A, 13B that output received signals (I_1, Q_1 and I_2, Q_2) by performing analog-digital conversion processing on the baseband signals (I, Q) obtained based on the radio signals to be generated. And, it is provided for each of the two branches, and the received signal (I_1, Q_1 and I_2, Q_2) is subjected to weight multiplication processing based on the tap coefficient (W_1 and W_2), and the tap output signal (Ti_1, Tq_1 and) The tap processing units 14A and 14B that output Ti_2, Tq_2) and the received signal vectors (V_1 and V_2) of the received signal, and the tap output signals (Ti_1, Tq_1 and Ti_2, Tq_2) and received signals of the two branches, respectively. An adaptive processing unit 15 that outputs tap coefficients (W_1 and W_2) based on vectors (V_1 and V_2), and a synthesis unit that diversifies the tap output signals of each of the two branches and outputs a composite signal (Ci, Cq). Diversity synthesis of 16 and the power detection unit 17 that outputs the phase rotation amount Δθ when the combined signal (Ci, Cq) has the maximum power, and the received signals (I_1, Q_1 and I_2, Q_2) of each of the two branches. It has a diversity synthesis unit 20 that outputs the composite reception signal (Ic, Qc), and a demodulation unit 21 that performs demographic processing on the composite reception signal (Ic, Qc), and is based on the phase rotation amount Δθ. After rotating the phase of the received signal (I_2, Q_2), the diversity synthesis unit 20 performs diversity synthesis to obtain a composite reception signal (Ic, Qc), and the composite reception signal (Ic, Qc) is demoted by the demodulation unit 21. I am trying to do it.

The wireless receiver 1 according to this embodiment has two branches corresponding to each of the two antennas as branches in the space diversity, and a mixer, an A / D converter, and a tap corresponding to each branch. Two processing units are provided for each.

The antennas 11A and 11B receive a radio signal transmitted from an antenna (not shown) of a fixed station on the transmitting side, and output a received wave signal corresponding to the received radio signal.

The mixers 12A and 12B receive the input of the received wave signal output from the antennas 11A and 11B, perform orthogonal demodulation processing on the received wave signal, and perform orthogonal demodulation processing on the received wave signal to perform the in-phase component baseband signal I and the orthogonal component baseband signal Q. Is output. In this embodiment, four-phase shift keying (QPSK: an abbreviation for Quadrature Phase Sheying) is used as the modulation method.

The A / D converter 13A of the first branch performs analog-digital conversion processing on the baseband signal I of the in-phase component output from the mixer 12A, outputs a received signal (in-phase component I_1), and is orthogonal. The baseband signal Q of the component is subjected to analog-to-digital conversion processing, and the received signal (orthogonal component Q_1) is output.

The A / D converter 13B of the second branch performs analog-digital conversion processing on the baseband signal I of the in-phase component output from the mixer 12B, outputs a received signal (in-phase component I_2), and is orthogonal. The baseband signal Q of the component is subjected to analog-to-digital conversion processing, and the received signal (orthogonal component Q_2) is output.

The tap processing unit 14A of the first branch has a weighting coefficient (tap coefficient and weight) corresponding to the signal on the first branch side output from the adaptive processing unit 15 with respect to the received signal output from the A / D converter 13A. Weight multiplication processing is performed based on (also called a vector), and a signal having an in-phase component and a signal having an orthogonal component are output. Specifically, the tap processing unit 14A of the first branch applies the weighting coefficient W_1 output from the adaptive processing unit 15 to the received signals (in-phase component I_1, orthogonal component Q_1) output from the A / D converter 13A. Multiply to generate a tap output signal (in-phase component Ti_1, orthogonal component Tq_1).

Then, the tap processing unit 14A of the first branch outputs the generated tap output signals (in-phase component Ti_1, orthogonal component Tq_1) to the adaptive processing unit 15 and the synthesis unit 16. The tap processing unit 14A of the first branch also uses the received signal (in-phase component I_1, orthogonal component Q_1) output from the A / D converter 13A as the received signal vector V_1 of the first branch with respect to the adaptive processing unit 15. Supply.

The tap processing unit 14B of the second branch has a weighting coefficient (tap coefficient and weight) corresponding to the signal on the second branch side output from the adaptive processing unit 15 with respect to the received signal output from the A / D converter 13B. Weight multiplication processing is performed based on (also called a vector), and a signal having an in-phase component and a signal having an orthogonal component are output. Specifically, the tap processing unit 14B of the second branch applies the weighting coefficient W_2 output from the adaptive processing unit 15 to the received signals (in-phase component I_2, orthogonal component Q_2) output from the A / D converter 13B. Multiply to generate a tap output signal (in-phase component Ti_2, orthogonal component Tq_2).

Then, the tap processing unit 14B of the second branch outputs the generated tap output signals (in-phase component Ti_2, orthogonal component Tq_2) to the adaptive processing unit 15 and outputs them to the synthesis unit 16. The tap processing unit 14B of the second branch also uses the received signals (in-phase component I_2, orthogonal component Q_2) output from the A / D converter 13B as the received signal vector V_2 of the second branch with respect to the adaptive processing unit 15. Supply.

The adaptation processing unit 15 performs adaptation equalization processing and executes tap update. Specifically, the adaptive processing unit 15 includes a reception signal vector V_1 and a tap output signal (in-phase component Ti_1, orthogonal component Tq_1) of the first branch output from the tap processing unit 14A of the first branch, and a second branch. The weighting coefficient W_1 and the second branch corresponding to the signal on the first branch side are used by using the received signal vector V_2 of the second branch and the tap output signal (in-phase component Ti_2, orthogonal component Tq_2) output from the tap processing unit 14B of the above. The weighting coefficient W_2 corresponding to the side signal is calculated.

Then, the adaptive processing unit 15 outputs the calculated weighting coefficient W_1 corresponding to the signal on the first branch side to the tap processing unit 14A of the first branch, and the weighting coefficient corresponding to the calculated signal on the second branch side. W_2 is output to the tap processing unit 14B of the second branch.

The synthesizing unit 16 diversifies the in-phase component and the orthogonal component of the signal of the system on the first branch side and the in-phase component and the orthogonal component of the signal of the system on the second branch side, and synthesizes the synthesized signal (in-phase component Ci, the orthogonal component Cq). ) Is output. The synthesis unit 16 inputs two signal sequences in parallel, synthesizes the two signal sequences by a predetermined synthesis method, and outputs the synthesized signal sequence of one system. In-phase synthesis is used as the synthesis method in the synthesis unit 16.

The power detection unit 17 obtains the phase rotation amount Δθ when the combined signal has the maximum power, based on the signal level of the combined signal (in-phase component Ci, orthogonal component Cq) output from the synthesis unit 16. Then, the power detection unit 17 outputs the obtained phase rotation amount Δθ to the phase adjustment unit 18 and outputs it to the mixer 19.

The phase adjusting unit 18 rotates the phase of the tap output signal (in-phase component Ti_2, orthogonal component Tq_2) output from the tap processing unit 14B of the second branch by the amount of rotation Δθ of the phase output from the power detection unit 17. A phase rotation signal (in-phase component Ri_2, orthogonal component Rq_2) is generated and output to the synthesis unit 16. That is, the synthesis unit 16 has a tap output signal (in-phase component Ti_1, orthogonal component Tq_1) output from the tap processing unit 14A of the first branch as a signal of the system on the first branch side, and a signal of the system on the second branch side. The phase rotation signal (in-phase component Ri_2, orthogonal component Rq_2) output from the phase adjusting unit 18 is diversified.

The mixer 19 rotates the phase of the received signal (in-phase component I_2, orthogonal component Q_2) output from the A / D converter 13B of the second branch by the amount of rotation Δθ of the phase output from the power detection unit 17. A phase adjustment signal (in-phase component Pi_2, orthogonal component Pq_2) is generated and output to the diversity synthesis unit 20. In the example shown in the figure, the mixer 19 is provided for the system on the second branch side, but the phase of the signal of the system on the first branch side and the phase of the signal of the system on the second branch side Is not limited to the configuration shown in the figure as long as it rotates by the relative rotation amount Δθ of the phase.

The diversity synthesizer 20 includes a received signal (in-phase component I_1, orthogonal component Q_1), which is a signal sequence output from the A / D converter 13A of the first branch, and a mixer 19 provided in the system on the second branch side. The phase adjustment signal (in-phase component Pi_2, orthogonal component Pq_2), which is a signal sequence output from the above, is diversified and the combined reception signal (in-phase component Ic, orthogonal component Qc) is output. The diversity synthesis unit 20 inputs two signal sequences in parallel, synthesizes the two signal sequences by a predetermined synthesis method, and outputs the synthesized signal sequence of one system. As the synthesis method in the diversity synthesis unit 20, the same synthesis method as the synthesis method in the synthesis unit 16 (that is, in-phase synthesis) is used.

The demodulation unit 21 receives an input of a composite reception signal (in-phase component Ic, orthogonal component Qc), which is a signal series output from the diversity synthesis unit 20, and modulates the composite reception signal (in-phase component Ic, orthogonal component Qc). As a method, demodulation processing is performed using four-phase shift keying (QPSK: an abbreviation for Quadrature Phase Sheying), and the signal sequence of the demodulation result is output.

Next, the operation, operation, and the like of the wireless receiving device 1 having such a configuration will be described.

As the processing related to the first branch, the received wave signal corresponding to the radio signal received by the antenna 11A is output to the mixer 12A, and the mixer 12A performs orthogonal demodulation processing on the received wave signal to perform the base band of the in-phase component. The signal I and the baseband signal Q of the orthogonal component are output to the A / D converter 13A, and the A / D converter 13A performs analog-digital conversion processing on the baseband signals I and Q to receive the received signal ( The in-phase component I_1 and the orthogonal component Q_1) are output to the tap processing unit 14A. The tap processing unit 14A performs weight multiplication processing on the received signal (in-phase component I_1, orthogonal component Q_1) using the weighting coefficient W_1 corresponding to the signal on the first branch side output from the adaptive processing unit 15. The tap output signal (in-phase component Ti_1, orthogonal component Tq_1) is output to the adaptive processing unit 15 and the synthesis unit 16.

As the processing related to the second branch, the received wave signal corresponding to the radio signal received by the antenna 11B is output to the mixer 12B, and the mixer 12B performs orthogonal demodulation processing on the received wave signal to perform the base band of the in-phase component. The signal I and the baseband signal Q of the orthogonal component are output to the A / D converter 13B, and the A / D converter 13B performs analog-digital conversion processing on the baseband signals I and Q to receive the received signal ( The in-phase component I_2 and the orthogonal component Q_2) are output to the tap processing unit 14B. The tap processing unit 14B performs weight multiplication processing on the received signal (in-phase component I_2, orthogonal component Q_2) using the weighting coefficient W_2 corresponding to the signal on the second branch side output from the adaptive processing unit 15. The tap output signal (in-phase component Ti_2, orthogonal component Tq_2) is output to the adaptive processing unit 15 and output to the synthesis unit 16.

Further, the tap processing unit 14A of the first branch supplies the received signal (in-phase component I_1, orthogonal component Q_1) as the received signal vector V_1 of the first branch to the adaptive processing unit 15, and the tap processing unit 14B of the second branch Supply the received signal (in-phase component I_2, orthogonal component Q_2) to the adaptive processing unit 15 as the received signal vector V_2 of the second branch.

Next, the adaptive processing unit 15 receives the tap output signal (in-phase component Ti_1, orthogonal component Tq_1), the reception signal vector V_1 of the first branch, the tap output signal (in-phase component Ti_2, the orthogonal component Tq_2), and the reception signal of the second branch. Using the vector V_2, the weighting coefficient W_1 corresponding to the signal on the first branch side and the weighting coefficient W_2 corresponding to the signal on the second branch side are calculated, and the tap processing unit 14A of the first branch and the tap processing of the second branch are performed. Output to unit 14B.

Further, the synthesis unit 16 has a signal of the system on the first branch side (specifically, the in-phase component Ti_1 and the orthogonal component Tq_1 of the tap output signal) and a signal of the system on the second branch side (specifically, the phase rotation signal). The in-phase component Ri_2 and the orthogonal component Rq_2) are diversified and the combined signal (in-phase component Ci, orthogonal component Cq) is output to the power detection unit 17, and the power detection unit 17 outputs the combined signal (in-phase component Ci, orthogonal component). Based on the signal level of Cq), the phase rotation amount Δθ when the combined signal has the maximum power is obtained and output to the phase adjusting unit 18 and the mixer 19, and the phase adjusting unit 18 taps the second branch. The phase of the tap output signal (in-phase component Ti_2, orthogonal component Tq_2) output from the processing unit 14B is rotated by the phase rotation amount Δθ, and the phase rotation signal (in-phase component Ri_2, orthogonal component Rq_2) is transmitted to the synthesis unit 16. Output.

Then, the mixer 19 rotates the phase of the received signal (in-phase component I_2, orthogonal component Q_2) by the amount of phase rotation Δθ, and outputs the phase adjustment signal (in-phase component Pi_2, orthogonal component Pq_2) to the diversity synthesizer 20. Then, the diversity synthesizer 20 has a received signal (in-phase component I_1, orthogonal component Q_1) which is a signal sequence of the system on the first branch side and a phase adjustment signal (in-phase component Pi_2, orthogonal) which is a signal sequence of the system on the second branch side. The component Pq_2) is diversified and the combined reception signal (in-phase component Ic, orthogonal component Qc) is output to the demodulation unit 21, and the demodulation unit 21 with respect to the combined reception signal (in-phase component Ic, orthogonal component Qc). The demodulation process is performed and the signal sequence of the demodulation result is output.

According to the wireless receiver 1 according to this embodiment, since the waveform is equalized with the signal obtained by the performance improvement effect of the received C / N ratio by the diversity synthesis, the received C / N ratio is lowered. It is possible to significantly improve the equalization performance in the environment, it is possible to perform highly accurate diversity synthesis, and it is possible to prevent the occurrence of deterioration of high multi-value demodulation in the signal after synthesis. .. According to the wireless receiver 1 according to this embodiment, the adaptive equalization process is incorporated into the power detection for phase adjustment of the diversity synthesis, and the power detection is performed after synthesizing the equalized signal. Therefore, it is possible to perform highly accurate phase control by eliminating the influence of interference due to reflected waves and delay error between antennas. According to the wireless receiver 1 according to this embodiment, since the purpose is further to detect power, high-precision equalization is not required, and an equalization algorithm that operates stably even when the reception C / N ratio is low. Can be adopted.

Next, the phase difference detection characteristics of the wireless receiver 1 having such a configuration will be verified with reference to FIGS. 2 and 3.

As shown in FIG. 2, when the signal transmitted from the single antenna 2 installed in the fixed station on the transmitting side is received by the two antennas 11A and 11B installed in the fixed station on the receiving side, One antenna 11A receives only the direct wave and outputs the received wave signal, and the other antenna 11B receives the received wave signal in a situation where fading is occurring (that is, it receives the reflected wave in addition to the direct wave). Under the condition that is output, the difference in correlation detection characteristics depending on the presence or absence of equalization processing is verified.

Here, verification is performed using the following specifications and conditions.
<Modulation method>
Four Phase Shift Keying (QPSK)
<Fading condition (minimum phase transition type)>
Delay time: 0.015T
Notch depth: 30 dB
Notch frequency: Modulation spectrum center frequency <equalization algorithm>
Godard's method (Goddard's Kalman algorithm)

In the signal sequence of the system on the second branch side between the signal sequence of the system on the first branch side based on the received wave signal of the antenna 11A and the signal sequence of the system on the second branch side based on the received wave signal of the antenna 11B. On the other hand, the correlation when the phase is rotated in the range of −180 ° to 180 ° is calculated, and this is set as detection 1. Detection 1 is a correlation detection result when there is no equalization process.

On the other hand, the signal sequence of the system on the first branch side based on the received wave signal of the antenna 11A and the signal sequence of the system on the second branch side based on the received wave signal of the antenna 11B are equalized and then equalized. The phase was rotated in the range of −180 ° to 180 ° with respect to the signal sequence of the system on the second branch side between the signal sequence of the system on the first branch side and the signal sequence of the system on the second branch side. The correlation between the cases is calculated, and this is designated as detection 2. Detection 2 is a correlation detection result when there is an equalization process.

Regarding detection 1 and detection 2, the relationship between the amount of phase rotation (that is, the phase difference) and the correlation is as shown in FIG. The vertical axis of FIG. 3 uses the average value between the phases of the in-phase components and the phases of the orthogonal components of the signal sequence of the system on the first branch side and the signal sequence of the system on the second branch side. Here, the correlation value is calculated by complex-multiplying one of the data for which the correlation is to be seen after taking the complex conjugate. According to this calculation, the imaginary number (IMG) component becomes 0 (zero) where the correlation is high.

From the result of detection 1 shown in FIG. 3, it can be confirmed that in the situation where fading occurs, the phase difference shifts and the detection sensitivity becomes low unless the equalization process is performed. On the other hand, from the result of detection 2, it can be confirmed that the phase difference can be detected and the detection sensitivity is high by performing the equalization process even in the situation where fading is occurring.

Although the embodiment of the present invention has been described above, the specific configuration is not limited to the above-described embodiment, and even if there is a design change or the like within a range that does not deviate from the gist of the present invention. Included in the invention. Specifically, the gist of the present invention is to incorporate an adaptive equalization process into the power detection for phase adjustment of diversity synthesis, synthesize the equalized signal, and then perform the power detection. Even if there is a design change within a range that does not deviate, it is included in the present invention. For example, in the above embodiment, the space diversity has two branches, a first branch and a second branch, but the number of branches is not limited to two, but two or more. Can be any number of.

1 Wireless receiver 11A antenna (1st branch)
11B antenna (second branch)
12A mixer (1st branch)
12B mixer (second branch)
13A A / D converter (1st branch)
13B A / D converter (second branch)
14A tap processing unit (1st branch)
14B tap processing unit (second branch)
15 Adaptation processing unit 16 Synthesis unit 17 Power detection unit 18 Phase adjustment unit 19 Mixer 20 Diversity synthesis unit 21 Demodulation unit

Claims (3)

A that is provided for each of a plurality of branches corresponding to each of the plurality of antennas, performs analog-to-digital conversion processing on the baseband signal obtained based on the radio signal received by the antenna, and outputs the received signal. / D converter and
A tap processing unit provided for each of the plurality of branches, which performs weight multiplication processing on the received signal based on the tap coefficient to output a tap output signal and outputs a received signal vector of the received signal.
An adaptive processing unit that outputs the tap coefficient based on the tap output signal and the received signal vector of each of the plurality of branches.
A compositing unit that diversifies the tap output signals of each of the plurality of branches and outputs a composite signal.
A power detector that outputs the amount of phase rotation when the combined signal has the maximum power, and
A diversity synthesizer that diversifies the received signals of each of the plurality of branches and outputs a composite received signal.
It has a demodulation unit that performs demodulation processing on the combined received signal.
After rotating the phase of the received signal based on the amount of rotation of the phase, the diversity synthesis unit performs diversity synthesis to obtain the combined reception signal, and the combined reception signal is demodulated by the demodulation unit.
A wireless receiver characterized by that. The modulation method of the radio signal received by the antenna is four-phase shift keying.
The wireless receiving device according to claim 1. The number of branches is two,
The wireless receiving device according to claim 1 or 2.

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