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WO1999043036A1 - Dephaseur et antenne a balayage - Google Patents

Dephaseur et antenne a balayage Download PDF

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Publication number
WO1999043036A1
WO1999043036A1 PCT/JP1999/000742 JP9900742W WO9943036A1 WO 1999043036 A1 WO1999043036 A1 WO 1999043036A1 JP 9900742 W JP9900742 W JP 9900742W WO 9943036 A1 WO9943036 A1 WO 9943036A1
Authority
WO
WIPO (PCT)
Prior art keywords
delay
phase shifter
phase
pair
amount
Prior art date
Application number
PCT/JP1999/000742
Other languages
English (en)
Japanese (ja)
Inventor
Naota Uenishi
Hiroshi Hayami
Yoshito Sakamoto
Akira Nishimura
Tamao Saito
Norichika Ohmi
Original Assignee
Sumitomo Electric Industries, Ltd.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Priority claimed from JP3883798A external-priority patent/JPH11239002A/ja
Priority claimed from JP5314598A external-priority patent/JPH11251823A/ja
Application filed by Sumitomo Electric Industries, Ltd. filed Critical Sumitomo Electric Industries, Ltd.
Publication of WO1999043036A1 publication Critical patent/WO1999043036A1/fr

Links

Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
    • H01Q3/34—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means
    • H01Q3/36—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means with variable phase-shifters
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/18—Phase-shifters
    • H01P1/181—Phase-shifters using ferroelectric devices
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/061—Two dimensional planar arrays
    • H01Q21/065—Patch antenna array

Definitions

  • the present invention relates to a phase shifter and a scanning antenna using the same. More specifically, the present invention relates to a phase shifter capable of controlling the amount of delay for delaying the phase of an electromagnetic wave of 1 THz or less, and to perform microwave communication with a mobile using the phase shifter. About the scanning antenna. Background art
  • phased array antennas for automatically tracking artificial satellites have been used in wireless communication systems using artificial satellites.
  • FIG. 13 is a plan view showing a configuration of such a conventional phased array antenna 70.
  • this phased array antenna 70 includes a plurality (35 in the figure) of antenna elements 71 arranged in a plurality of rows and a plurality of columns (five rows and seven columns in the figure).
  • Each row is provided with a sub-waveguide 72 extending in the X-axis direction in the figure, and each sub-waveguide 72 is connected to a group of antenna elements 71 in the corresponding row.
  • a phase shifter 74 is provided inside one end of each sub waveguide 72, and one end of each sub waveguide 72 is connected to a main waveguide 73 extending in the Y-axis direction in the figure. ing.
  • Microwave ⁇ for communication is input and output from one end of main waveguide 73.
  • the microwave ct refers to an electromagnetic wave of l GHz to 1 T Hz.
  • the phase shifter 74 includes a plurality of (four in the figure) toroids 81 to 84 arranged along the central axis of the sub-waveguide 72.
  • the toroids 81 to 84 are formed of ferrimagnetic material, and are sequentially doubled in length.
  • Drive wires 85 to 88 are inserted through the toroids 81 to 84, respectively.
  • the toroids 81 to 84 are magnetized, the magnetic permeability in the sub-waveguide 72 changes, and the phase of the microwave is delayed.
  • Each of the magnetized toroids 81 to 84 has a phase of microwave ⁇ of 22. 5 °, 45 °, 90. , 180 ° delay. Therefore, by changing the combination of the pins 85 to 88 through which the pulse current flows, the phase delay amount of the microwave can be adjusted in a unit of 22.5 ° in the range of 0 to 360 °.
  • phase delay amount of the phase shifters 74 in each row By adjusting the phase delay amount of the phase shifters 74 in each row, the phase of the microwaves emitted from the antenna elements 7 in each row can be adjusted, and the phase of the phased array antenna 70 can be adjusted.
  • the direction of the generated microwave beam can be adjusted within the ⁇ ⁇ plane.
  • phased array antenna 70 is provided rotatable about the ⁇ axis in the figure, and is rotatable by a desired angle from a reference position by a mechanical driving device (not shown). Therefore, the direction of the beam emitted from the entire phased array antenna 70 can be adjusted even in the plane.
  • phased array antenna 70 When the artificial satellite is in the ⁇ -axis direction, the phase delay amounts of the five phase shifters 74 are set to the same value. As a result, the microwaves are radiated from all the antenna elements 71 in the same phase, and the beam of the microwaves is radiated to the satellite in the ⁇ -axis direction.
  • the phase delay amounts of the five phase shifters 74 are sequentially shifted toward the ⁇ -axis positive direction by a value corresponding to the angle. Set to be larger.
  • the phase of the microphone mouth wave ⁇ emitted from the antenna element 71 located in the ⁇ -axis positive direction lags behind the phase of the microwave ⁇ emitted from the antenna element 71 located in the ⁇ -axis negative direction,
  • the beam of the microwave a is emitted to the satellite at an angle corresponding to the difference in the amount of phase delay between the phase shifters 74 from the Z-axis direction to the Y-axis positive direction.
  • the phase delay amounts of the five phase shifters 74 are sequentially shifted toward the Y-axis positive direction by a value corresponding to the angle. It is set to be smaller.
  • the phase of the microphone mouth wave ⁇ emitted from the antenna element 71 located in the positive Y-axis direction leads the phase of the microwave ⁇ emitted from the antenna element 71 located in the negative Y-axis direction
  • the beam of the microwave ⁇ is emitted to the satellite at an angle corresponding to the difference in the amount of phase delay between the phase shifters 74 from the ⁇ -axis direction to the ⁇ -axis negative direction.
  • the phased array antenna 70 is rotated by that angle about the Y-axis by a mechanical driving device.
  • the phase shifter 74 and the driving device are automatically controlled so that the microwave ⁇ beam always faces the satellite.
  • FIG. 15 is a circuit diagram showing a configuration of another conventional phase shifter 90.
  • this phase shifter 90 is used in a system in which microwaves are transmitted by a microstrip line, and is connected in series between input / output terminals 90a and 90b. And four (in the figure, four) diodes 91 to 94, and microstrip lines 95 to 98 connected in parallel to the diodes 91 to 94, respectively.
  • Each of the diodes 91 to 94 is provided with a DC power supply (not shown) for applying a forward bias voltage to the corresponding diode to make it conductive.
  • Each of the microstrip lines 95 to 98 is twice as long in order, and delays the phases of the microwaves by 22.5 °, 45 °, 90 °, and 180 °, respectively. Therefore, by changing the combination of the diodes 41 to 44 to be made conductive, the phase delay amount of the microphone mouth wave can be adjusted in the unit of 22.5 ° in the range of 0 to 360 °.
  • phase shifter 74 consisting of toroids 81 to 84 made of ferrimagnetic material is used, so the device size becomes large and the device weight becomes large. There was a problem of becoming. Also, a high-output pulse current generator is required for each of the drive wires 85 to 88 of each phase shifter 74, which has increased the cost of the system.
  • phase delay of the phase shifter 74 could be adjusted only in 22.5 ° units, and the beam emission direction could not be adjusted continuously.
  • the amount of phase delay can be adjusted at a smaller angle, but more pulse generators are required and the cost increases.
  • phase shifter 74 since only one phase shifter 74 is provided at one end of each sub-waveguide 72, the beam emission direction can be adjusted only in the YZ plane, and the beam emission direction can be adjusted. Can not be adjusted in the XZ plane. For this reason, a mechanical driving device for adjusting the beam emission direction in the XZ plane is required, which increases costs. I was If a phase shifter 74 is provided between every two adjacent antenna elements 71 in each sub-waveguide 72, the beam emission direction can be adjusted even in the XZ plane, but more A pulse current generator is required, which further increases the cost.
  • phase shifter 40 of FIG. 15 since long microstrip lines 95 to 98 were used, there was a problem that the device size became large. In addition, a plurality of DC power supplies for controlling the diodes 91 to 94 to conduct and non-conduct, and their control devices were required, and the system cost increased.
  • this phase shifter 90 could also adjust the phase delay amount only in 22.5 ° units, and could not continuously adjust the phase delay amount. If the number of microstrip lines 95 to 98 is increased, the amount of phase delay can be adjusted at a smaller angle, but more pulse generators and the like are required and the cost is reduced.
  • a first object of the present invention is to provide a compact phase shifter capable of continuously adjusting the amount of phase delay, reducing the cost of the system, and providing a compact phase shifter.
  • a second object of the present invention is to provide a lightweight and compact scanning antenna capable of continuously adjusting the beam emission direction, reducing the cost of the system, and providing a light and compact scanning antenna. Disclosure of the invention
  • the present invention relates to a phase shifter capable of controlling a delay amount for delaying the phase of an electromagnetic wave of 1 THz or less, provided opposite to each other, transmitting the electromagnetic wave, and A pair of transmission lines to which a control voltage of a frequency lower than the electromagnetic wave for controlling the amount of delay is applied, and insulation provided between a pair of transmission lines and whose dielectric constant changes according to the control voltage It is provided with a sexual substance.
  • Another invention is a scanning antenna for performing microwave communication with a moving object, comprising: a plurality of antenna elements arranged in a plurality of rows and a plurality of columns; and a plurality of antenna elements provided between each of the plurality of rows.
  • Phase shifter that can control the amount of delay to delay the microwave phase given to the antenna element and apply it to the succeeding antenna element Is provided.
  • the first phase shifters are provided opposite to each other, transmit microwaves, and a first control voltage having a lower frequency than the microwaves for controlling the amount of delay between one and the other is provided.
  • a pair of transmission lines to be applied, and an insulating material provided between the pair of transmission lines, the dielectric constant of which is changed according to the first control voltage.
  • another invention is provided between the plurality of rows, and is capable of controlling the amount of delay for delaying the phase of the microwave given to the front row antenna element and giving it to the rear row antenna element.
  • the second phase shifters are provided opposite to each other, transmit microwaves, and have a second control voltage having a lower frequency than the microwaves for controlling the amount of delay between one and the other.
  • a pair of transmission lines to which is applied, and an insulating material provided between the pair of transmission lines and having a dielectric constant that changes according to a second control voltage.
  • the insulating material of the first and second phase shifters includes a ferroelectric material, an antiferroelectric material, or a liquid crystal material.
  • a ferroelectric substance, an antiferroelectric substance, or a liquid crystal substance is formed into fine particles and dispersed in a polymer.
  • the first and second control voltages are DC voltages.
  • FIG. 1 is a block diagram showing a configuration of a main part of a wireless communication system according to a first embodiment of the present invention.
  • FIG. 2 is a perspective view showing the configuration of the scanning antenna shown in FIG.
  • FIG. 3 is a perspective view showing the configuration of the phased array antenna shown in FIG.
  • FIG. 4 is a perspective view showing the configuration of the phase shifter shown in FIG.
  • FIG. 5 is a sectional view taken along line AA ′ of FIG.
  • FIG. 6 is a diagram showing the electric field strength dependence of the phase delay rate in the phase shifter shown in FIG.
  • FIG. 7 is a circuit block diagram showing the configuration of the frequency converter 16 shown in FIG. 8A and 8B are circuit block diagrams showing the configuration of the frequency converter 17 shown in FIG.
  • FIG. 9 is a circuit diagram showing a configuration of the switching circuit shown in FIG.
  • FIG. 10 is a sectional view showing a configuration of a phase shifter in a wireless communication system according to a second embodiment of the present invention.
  • FIG. 11 is a diagram showing the electric field strength dependence of the phase delay rate in the phase shifter shown in FIG.
  • FIG. 12 is a sectional view showing an improved example of the phase shifter shown in FIG.
  • FIG. 13 is a plan view showing a configuration of a conventional phased array antenna.
  • FIG. 14 is a perspective view showing the configuration of the phase shifter shown in FIG.
  • FIG. 15 is a circuit diagram showing another example of the phase shifter. BEST MODE FOR CARRYING OUT THE INVENTION
  • FIG. 1 is a block diagram showing a configuration of a main part of a wireless communication system according to a first embodiment of the present invention.
  • this wireless communication system is a system using two artificial satellites, including a scanning antenna 10, an interface device 11, signal input terminals 12, 13, and a signal input / output. It has terminals 14, controller 15, frequency converters 16 and 17, and switching circuit 18.
  • the scanning antenna 10 includes six trapezoidal phased array antennas 1 to 6 and one hexagonal phased array antenna 7 as shown in FIG.
  • the length of one side of the hexagon is equal to the length of the top side of the trapezoid, and the seven antennas 1 to 7 are trapezoidal so that the trapezoidal antennas 1 to 6 support the hexagonal antenna 7 horizontally.
  • Assembled in The assembled antennas 1 to 7 are covered with a hemispherical cover 8.
  • Antenna 7 tracks one satellite moving within 40 ° from the zenith.
  • Each of antennas 1 to 6 tracks a satellite that moves horizontally 60 to 80 degrees from the zenith.
  • Two of the antennas 1 to 7 track the satellite one by one, and when the satellite moves and exceeds the trackable range of the antenna, another antenna tracks the satellite.
  • FIG. 3 is a perspective view showing a configuration of one phased array antenna 1.
  • this phased array antenna 1 is composed of a plurality of (3 5 in the figure) antenna elements 2 arranged in a plurality of rows and a plurality of columns (5 rows and 7 columns in the figure) on a rectangular substrate 21. 2 is provided.
  • Each row is provided with a sub-microstrip line 23 extending in the X-axis direction in the figure, and the metal strip of each sub-microstrip line 23 is connected to a group of antenna elements 22 in the corresponding row.
  • One end of each sub microstrip line 23 is connected via a capacitor 24 to a main microstrip line 25 extending in the Y-axis direction in the figure.
  • One end of the main microstrip line 25 is an input / output terminal via a capacitor 24.
  • each sub-microstrip line 23 is connected to a DC power supply terminal 29 via a coil 27.
  • Microwave ⁇ is input and output from input / output terminal 26. Variable DC voltages are separately applied to the DC power supply terminals 28 and 29, respectively.
  • the capacitor 24 is a high-pass filter for preventing a DC current from flowing between the main microstrip line 25 and the sub-microstrip line 23.
  • the coil 27 is a low-pass filter for preventing microwaves from entering the DC power supply terminals 28 and 29. Therefore, it is possible to separately apply a DC voltage to the main microstrip line 25 and the sub-microstrip line 23 from the DC power supply terminals 28 and 29.
  • phase shifter 30 is connected in the middle of the sub-microstrip line 23 between each two adjacent antenna elements 22, and is connected between one end of each two adjacent sub-microstrip lines 23.
  • a phase shifter 30 is connected in the middle of the main microstrip line 25.
  • FIG. 4 is a perspective view showing the configuration of the phase shifter 30, and FIG. 5 is a cross-sectional view taken along the line ⁇ -A 'of FIG.
  • this phase shifter 30 has a ferroelectric layer
  • Ferroelectric layer 3 2 is specifically a B a T i 0 3, L i N B_ ⁇ 3, L i T a 0 monocrystalline layer or polycrystalline layer such as 3.
  • the phase shifter 30 is different from the ordinary microstrip lines 23 and 25 in that the insulating layers of the microstrip lines 23 and 25 are replaced with ferroelectric layers 32.
  • an insulating layer is provided between the metal plate and the metal strip, and this insulating layer keeps the distance between the metal plate and the metal strip constant, thereby keeping the characteristic impedance of the line constant. Will be kept.
  • a material of the insulating layer a material having a structurally sufficient strength, a small loss of microwave, and a dielectric constant f which does not change even when a DC voltage is applied, specifically, FRP, Teflon Is selected.
  • the phase shifter 30 positively utilizes the fact that when a DC voltage is applied to the ferroelectric layer 32, the dielectric constant ⁇ changes according to the magnitude of the DC voltage. That is, when the microwave ⁇ propagates through the ferroelectric layer 32, the phase delay ⁇ of the microwave ⁇ becomes the square of the dielectric constant f of the ferroelectric layer 32 as shown by the following equation. Is proportional to
  • L is the length of the ferroelectric layer 32
  • ⁇ 0 is the wavelength of the microwave ⁇ propagating in free space
  • ⁇ is the wavelength when the microwave ⁇ propagates in the ferroelectric layer 32. is there. Therefore, by adjusting the direct current voltage applied to the ferroelectric layer 32 to adjust the dielectric constant ⁇ of the ferroelectric layer 32, the phase delay amount ⁇ of the microwave ⁇ can be adjusted.
  • FIG. 6 is a diagram illustrating the electric field strength (kVZmm) dependency of the phase delay rate (degZmm) of the phase shifter 30.
  • the ferroelectric layer 3 to form a single crystal layer of the B a T i ⁇ 3.
  • the frequency of the microwave was set to 20 GHz.
  • the phase delay rate (deg Zmm) is obtained by dividing the phase delay amount ⁇ of the microwave generated by passing through the phase shifter 30 by the line length L of the phase shifter 30.
  • the metal plate 3 1 is grounded, the coil 27 and the variable DC power supply 3 4 are connected in series between the metal strip 3 3 and the metal plate 3 1, and the electric field strength of the ferroelectric layer 3 2 (k VZm m) was adjusted.
  • the electric field strength (k VZ mm) is obtained by dividing the DC voltage between the metal strip 33 and the metal plate 31 by the thickness of the ferroelectric layer 32.
  • the phase delay rate (deg / mm) gradually decreased from 17 to 10. Therefore, it was found that if the line length L of the phase shifter 30 is 1 mm, the phase delay amount can be changed by 4 ° by changing the DC voltage by about 500 V.
  • phased array antenna 1 When the human satellite is in the Z-axis direction, the phase delay ⁇ of all phase shifters 30 is set to 360 °. As a result, the microwaves ⁇ are radiated in phase from all the antenna elements 71, and the beam of the microwaves ⁇ emitted from the entire antenna 1 is directed in the ⁇ -axis direction.
  • the phase delay 0 of the four phase shifters 30 provided on the main microstrip line 25 depends on the angle. Is set to a value that deviates from 360 ° As a result, the difference between the phase of the microwave ⁇ emitted from the antenna element 22 located in the negative ⁇ axis direction and the phase of the microwave ⁇ emitted from the antenna element 22 located in the positive ⁇ axis direction is reduced. The resulting beam of microwave ⁇ is emitted from the ⁇ -axis direction to the ⁇ -axis direction by an angle corresponding to the phase delay ⁇ of the phase shifter 30 and emitted to the satellite.
  • the phase delay ⁇ of the six phase shifters 30 provided in each sub-microstrip line 23 depends on the angle.
  • the value is set to a value that is shifted by 360 °.
  • the difference between the phase of the microwave ct emitted from the antenna element 22 located in the negative direction of the X axis and the phase of the microwave ⁇ emitted from the antenna element 22 located in the positive direction of the X axis is determined.
  • the microwave beam is emitted to the satellite at an angle corresponding to the phase delay ⁇ of the phase shifter 30 from the ⁇ -axis direction to the X-axis direction.
  • the phase delay ⁇ of the phase shifter 30 is automatically controlled so that the beam of the microwave ⁇ is directed to the artificial satellite.
  • phase of the microwave ⁇ incident on each of the 35 antenna elements 22 with a different phase is adjusted by adjusting the phase delay amount ⁇ of each phase shifter 30. And can be led to the input / output terminal 26. Thereby, the receiving sensitivity can be improved.
  • the other phased array antennas 2 to 7 are the same as phased array antenna 1.
  • control device 15 controls the entire system according to a control signal input from the outside via the interface device 11.
  • the frequency converter 16 converts the microwave RF S 1 received by one of the seven phased array antennas 1 to 7 into an intermediate frequency signal IFS 1 by heterodyne conversion to enable high-sensitivity reception. It is. More specifically, the frequency converter 16 includes a low-noise amplifier 40, a mixer 41, an IF amplifier 42, and a multiplier 43, as shown in FIG.
  • the 22 GHz microwave RF S 1 received by one of the seven phased array antennas 1 to 7 is amplified by the low noise amplifier 40.
  • Multiplier 43 is a 2.5 GHz port provided externally through signal input terminal 13 —a cull signal LS 0 is an integer multiple of 2 OGHz local signal LS 1 and 30 GHz local signal Generate LS2.
  • the oral signals LSI, LS2 are also supplied to a frequency converter 17.
  • the mixer 41 mixes the output signal R F S 1 of the low noise amplifier 40 and the local signal L S 1 generated by the multiplier 43 to generate a 2 GHz intermediate frequency signal I F S 1.
  • the output signal IF S1 of the mixer 41 is amplified by the IF amplifier 42 and output to the signal output terminal 12.
  • the frequency converter 17 is coupled to an antenna other than the antenna coupled to the frequency converter 16, and the microwave RF S2 received by the antenna is heterodyne-converted into an intermediate frequency signal IFS2 to enable high-sensitivity reception.
  • the intermediate frequency signal IFS3 is converted to microwave RFS3 and given to the antenna.
  • the frequency converter 17 specifically includes a low-noise amplifier 44, mixers 45 and 48, IF amplifiers 46 and 47, and a high-power amplifier 49, as shown in FIGS. 8A and 8B.
  • the 22 GHz microwave RFS 2 received by the antenna is amplified by the low noise amplifier 44.
  • the mixer 45 mixes the output signal RF S 2 of the low noise amplifier 44 with the oral signal LS 1 generated by the frequency converter 16 to generate a 2 GHz intermediate frequency signal IFS 2.
  • the output signal IFS 2 of mixer 45 is I The signal is amplified by the F amplifier 46 and output to the signal input / output terminal 14.
  • the IF amplifier 47 amplifies the 3 GHz intermediate frequency signal IFS 3 externally supplied through the signal input / output terminal 14.
  • the mixer 48 mixes the output signal IF S3 of the IF amplifier 47 with the local signal L S2 generated by the frequency converter 16 to generate a microwave R F S 3 of 33 GHz.
  • the output signal R F S 3 of the mixer 48 is amplified by the high power amplifier 49 and supplied to the antenna.
  • the switching circuit 18 is controlled by the controller 15 and connects one of the seven phased array antennas 1 to 7 to the frequency converter 16 and the other antenna. To the frequency converter 17.
  • the switching circuit 18 includes switches 51 to 59 as shown in FIG.
  • the common terminals 51c to 57c of the switches 51 to 57 are connected to the phased array antennas 1 to 7, respectively.
  • One of the switching terminals 51a to 57a of the switches 51 to 57 is connected to the switching terminals 58a to 58g of the switch 58, respectively.
  • the other switching terminals 51 b to 57 b of the switches 51 to 57 are respectively connected to the switching terminals 59 a to 59 g of the switch 59.
  • the common terminals 58 h and 59 h of the switches 58 and 59 are connected to the frequency converters 17 and 16, respectively.
  • Switches 51-59 are actually generated by diodes and controlled by controller 15.
  • FIG. 9 illustrates an example in which antenna 1 is connected to frequency converter 17 via switches 51 and 58, and antenna 7 is connected to frequency converter 16 via switches 57 and 59. Is done.
  • Two of the seven phased array antennas 1 to 7 facing the target two artificial satellites are connected to the frequency converters 16 and 17 by the switching circuit 18.
  • the phase delay ⁇ of the phase shifter 30 of each antenna is continuously adjusted, and the beam emission direction of each antenna is always directed toward the satellite. If the human satellite moves out of the tracking range of the antenna, another antenna is connected to the frequency converter 16 or 17 instead of that antenna.
  • the microphone mouth wave RFS 1 received by one of the two antennas is heterodyne-converted into an intermediate frequency signal IFS 1 by the frequency converter 16, and high-sensitivity reception Is performed.
  • the microphone mouth wave RFS 2 received by the other of the two antennas is heterodyne-converted into an intermediate frequency signal IFS 2 by the frequency converter 17, and high-sensitivity reception is performed.
  • the signals IFS 1 and IFS 2 are converted into information by a signal-to-information converter (not shown).
  • the intermediate frequency signal IFS 3 on which the information is superimposed is converted into a microwave RFS 3 by the frequency converter 17, and the microwave RFS 3 is radiated to the satellite via the other of the two antennas.
  • the insulating layer of the microstrip line is replaced with a ferroelectric layer 32 to constitute a phase shifter 30, and a phase shifter 30 is provided between a metal strip 33 and a metal plate 31.
  • the phase delay ⁇ is adjusted by adjusting the DC voltage of. Therefore, the size of the device and the weight of the device can be reduced as compared with the related art in which the phase shifter 74 is configured by the toroids 81 to 84 of the ferrimagnetic material.
  • phase delay amount 0 is continuously adjusted instead of the conventional 22.5 ° unit. Can be adjusted.
  • phase delay amount ⁇ can be controlled only by the small power variable DC power supply 34, the cost of the system can be reduced as compared with the conventional system that required a high-output pulse current generator.
  • phase shifters 30 are arranged in the X-axis direction and the Y-axis direction in the phased array antenna 1, the beam emission direction can be changed not only in the YZ plane but also in the XZ plane. Therefore, the cost of the system can be reduced as compared with the conventional system in which the beam emission direction is changed in the XZ plane by a mechanical driving device.
  • a single crystal layer of Ba Ti 0 3 is used as a specific example of the ferroelectric layer 32 of the phase shifter 30.
  • the present invention is not limited to Ba Ti 3. Any ferroelectric material is acceptable.
  • L i N b ⁇ 3 or L i T a ⁇ 3 may be used.
  • a polycrystalline layer may be used instead of a single crystal layer.
  • ferroelectric material it is not necessary to use a ferroelectric material as long as it is an insulating material whose dielectric constant E changes with the electric field strength.
  • it may be in the antiferroelectric such as P b Z r 0 3, may be a liquid crystal material.
  • a DC power is applied between the metal strip 33 and the metal flat plate 31.
  • the voltage is not limited to the DC voltage, and may be an AC voltage as long as the voltage has a frequency lower than the microwave ⁇ .
  • the phase delay ⁇ of the microwave ⁇ can be adjusted by adjusting the amplitude and frequency of the AC voltage.
  • FIG. 10 is a cross-sectional view showing a configuration of a phase shifter 60 of a fused array antenna used in a wireless communication system according to a second embodiment of the present invention, and is a diagram to be compared with FIG. .
  • the phase shifter 60 in FIG. 10 differs from the phase shifter 30 in FIG. 5 in that the ferroelectric layer 32 is replaced by ferroelectric fine particles / polymer dispersion layer 61.
  • the reason that the ferroelectric material is made into fine particles and dispersed in a polymer is to simplify the manufacturing method and to change the component ratio of the fine particles 62 and the polymer 63 to a desired value for the phase delay rate (deg Zmm). This is for adjustment.
  • FIG. 11 is a diagram illustrating the dependence of the phase delay rate (deg Zmm) of the phase shifter 60 on the electric field strength (kV / mm). Strength using single-crystal particles of B a T i 0 3 of diameter 1 zm as dielectric grains 6 2, and the fine particles 6 2 to form a dispersion layer 61 are dispersed in the polymer 6 3. The component ratio of the fine particles 62 / polymer 63 was 80%.
  • phase delay rate (deg / mm) When the electric field strength (kVZmm) was increased from 0 to 1.0, the phase delay rate (deg / mm) gradually decreased from 0.2 to 0.05. Therefore, it was found that if the line length L of the phase shifter 60 was set to 1 O mm and the DC voltage was changed by about 1 kV, the phase delay ⁇ could be changed by 1.5 °. Further, it was found that the phase delay rate (deg Zmm) was reduced to about 100, compared to the first embodiment. In addition, if the component ratio of the fine particles 62 and the polymer 63 is changed, the phase delay rate (deg / mm) is considered to change.
  • the same effects as those of the first embodiment can be obtained.
  • the dispersion layer 61 in which the ferroelectric fine particles 62 are dispersed in the polymer 63 is used, the ferroelectric It can be manufactured more easily than in the first embodiment using a single crystal layer. Further, by adjusting the component ratio of the fine particles 62 and the polymer 63, the phase delay rate can be adjusted.
  • a ferroelectric layer 66 and a volima layer 67 may be alternately stacked between the metal strip 33 and the metal flat plate 31.
  • the phase delay rate can be easily adjusted by adjusting the film thickness ratio of the ferroelectric layer 66 / polymer layer 67. Can be adjusted.
  • an insulating substance for controlling the amount of delay is arranged between a pair of transmission lines provided to face each other for transmitting electromagnetic waves, By applying a low-frequency control voltage to a pair of transmission lines and adjusting the control voltage, the amount of phase delay can be continuously adjusted. If this phase shifter is arranged between antenna elements arranged in a plurality of rows and a plurality of columns, the direction of the beam of the micro mouth wave emitted from the entire scanning antenna can be continuously adjusted.

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  • Variable-Direction Aerials And Aerial Arrays (AREA)

Abstract

L'invention porte sur un déphaseur (1) comprenant une couche (3) ferroélectrique formée sur une première plaque (2) métallique, et une bande (4) métallique formée sur la couche ferroélectrique. Lorsqu'il y a variation de tension en courant continu entre la bande (4) métallique et la plaque (2) métallique plate, la constante diélectrique de la couche (3) ferroélectrique change. Par conséquent, le temps de propagation de phase de l'hyperfréquence (α) peut varier en continu par réglage du courant continu. Ce déphaseur (1) est placé entre les rangées et les colonnes d'une pluralité d'éléments (22) d'antenne de façon à former une antenne réseau à commande de phase.
PCT/JP1999/000742 1998-02-20 1999-02-18 Dephaseur et antenne a balayage WO1999043036A1 (fr)

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
JP3883798A JPH11239002A (ja) 1998-02-20 1998-02-20 移相器
JP10/38837 1998-02-20
JP10/53145 1998-03-05
JP5314598A JPH11251823A (ja) 1998-03-05 1998-03-05 走査アンテナ

Publications (1)

Publication Number Publication Date
WO1999043036A1 true WO1999043036A1 (fr) 1999-08-26

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Application Number Title Priority Date Filing Date
PCT/JP1999/000742 WO1999043036A1 (fr) 1998-02-20 1999-02-18 Dephaseur et antenne a balayage

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Country Link
WO (1) WO1999043036A1 (fr)

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2001020720A1 (fr) * 1999-09-14 2001-03-22 Paratek Microwave, Inc. Antennes reseaux a commande de phase alimentees en serie a dephaseurs dielectriques
WO2005057718A1 (fr) * 2003-12-10 2005-06-23 Telefonaktiebolaget Lm Ericsson (Publ) Boucle a verrouillage de retard a retard commande avec precision
CN103956538B (zh) * 2014-04-29 2016-05-11 中国人民解放军国防科学技术大学 一种基于石墨烯的低损耗介质移相器
EP4148899A4 (fr) * 2020-05-06 2024-06-05 Time Varying Transmission Co., Ltd Unité de déphasage, unité d'antenne, unité de réseau à commande de phase et réseau à commande de phase

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JPS5418754B2 (fr) * 1972-09-25 1979-07-10
JPH02225357A (ja) * 1989-02-23 1990-09-07 Matsushita Electric Works Ltd 複合誘電体
JPH04161461A (ja) * 1990-10-24 1992-06-04 Murata Mfg Co Ltd 誘電体起電流型アンテナ用複合材料
JPH04245803A (ja) * 1990-08-24 1992-09-02 Hughes Aircraft Co 強化されたマイクロ波複屈折性を有する液晶ベース複合材料
JPH05243804A (ja) * 1992-02-29 1993-09-21 Nec Corp マイクロストリップライン
US5589845A (en) * 1992-12-01 1996-12-31 Superconducting Core Technologies, Inc. Tuneable electric antenna apparatus including ferroelectric material

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Publication number Priority date Publication date Assignee Title
JPS5418754B2 (fr) * 1972-09-25 1979-07-10
JPH02225357A (ja) * 1989-02-23 1990-09-07 Matsushita Electric Works Ltd 複合誘電体
JPH04245803A (ja) * 1990-08-24 1992-09-02 Hughes Aircraft Co 強化されたマイクロ波複屈折性を有する液晶ベース複合材料
JPH04161461A (ja) * 1990-10-24 1992-06-04 Murata Mfg Co Ltd 誘電体起電流型アンテナ用複合材料
JPH05243804A (ja) * 1992-02-29 1993-09-21 Nec Corp マイクロストリップライン
US5589845A (en) * 1992-12-01 1996-12-31 Superconducting Core Technologies, Inc. Tuneable electric antenna apparatus including ferroelectric material

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2001020720A1 (fr) * 1999-09-14 2001-03-22 Paratek Microwave, Inc. Antennes reseaux a commande de phase alimentees en serie a dephaseurs dielectriques
US6377217B1 (en) 1999-09-14 2002-04-23 Paratek Microwave, Inc. Serially-fed phased array antennas with dielectric phase shifters
WO2005057718A1 (fr) * 2003-12-10 2005-06-23 Telefonaktiebolaget Lm Ericsson (Publ) Boucle a verrouillage de retard a retard commande avec precision
US7456664B2 (en) 2003-12-10 2008-11-25 Telefonaktiebolaget Lm Ericsson (Publ) Delay locked loop with precision controlled delay
CN103956538B (zh) * 2014-04-29 2016-05-11 中国人民解放军国防科学技术大学 一种基于石墨烯的低损耗介质移相器
EP4148899A4 (fr) * 2020-05-06 2024-06-05 Time Varying Transmission Co., Ltd Unité de déphasage, unité d'antenne, unité de réseau à commande de phase et réseau à commande de phase
US12327924B2 (en) 2020-05-06 2025-06-10 Time Varying Transmission Co., Ltd. Phase-shifting unit, antenna unit, phased array unit and phased array

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