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WO2018189905A1 - Base station, terminal, transmission program, reception program, transmission method, and reception method - Google Patents

Base station, terminal, transmission program, reception program, transmission method, and reception method Download PDF

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Publication number
WO2018189905A1
WO2018189905A1 PCT/JP2017/015374 JP2017015374W WO2018189905A1 WO 2018189905 A1 WO2018189905 A1 WO 2018189905A1 JP 2017015374 W JP2017015374 W JP 2017015374W WO 2018189905 A1 WO2018189905 A1 WO 2018189905A1
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Prior art keywords
signals
signal
radio resource
bandwidth
transmission
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PCT/JP2017/015374
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French (fr)
Japanese (ja)
Inventor
ジヤンミン ウー
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富士通株式会社
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Priority to PCT/JP2017/015374 priority Critical patent/WO2018189905A1/en
Publication of WO2018189905A1 publication Critical patent/WO2018189905A1/en

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes

Definitions

  • the present invention relates to a base station, a terminal, a transmission program, a reception program, a transmission method, and a reception method.
  • CSI is an abbreviation for Channel State Information.
  • a technique for generating a channel for a multi-antenna using wavelet transform is known (see, for example, Patent Documents 1 to 3 below).
  • an object of the present invention is to provide a base station, a terminal, a transmission program, a reception program, a transmission method, and a reception method that can improve transmission quality without feedback of channel state information. To do.
  • the product of the time length and the bandwidth in the radio resource unit to which data is allocated is the same, and the time length and the bandwidth in the radio resource unit A base station, a transmission program, and a transmission comprising: a generation unit that generates a plurality of signals with different combinations of widths by inverse wavelet transform; and a plurality of antennas that respectively transmit the plurality of signals generated by the generation unit A method is proposed.
  • the product of the time length and the bandwidth in the radio resource unit to which the data is allocated is the same, and the combination of the time length and the bandwidth in the radio resource unit is different from each other.
  • a receiving unit that generates a signal by inverse wavelet transform, receives the plurality of signals from a base station that transmits the generated plurality of signals by a plurality of antennas, and a decoding unit that decodes the signals received by the receiving unit A terminal, a receiving program, and a receiving method are proposed.
  • the present invention has an effect that transmission quality can be improved without feedback of channel state information.
  • FIG. 1 is a diagram illustrating an example of a communication system according to an embodiment.
  • FIG. 2 is a diagram illustrating an example of a subcarrier, a transmission slice, and a transmission block according to the embodiment.
  • FIG. 3 is a diagram illustrating an example of noise received by the receiving apparatus according to the embodiment.
  • FIG. 6 is a diagram illustrating an example of the transmitter of the transmission apparatus according to the embodiment.
  • FIG. 7 is a diagram illustrating an example of a receiver of the receiving apparatus according to the embodiment.
  • FIG. 8 is a diagram illustrating an example of a relationship between the SNR and the symbol error rate according to the embodiment.
  • FIG. 9 is a diagram illustrating another example of the relationship between the SNR and the symbol error rate according to the embodiment.
  • FIG. 10 is a diagram illustrating still another example of the relationship between the SNR and the symbol error rate according to the embodiment.
  • FIG. 1 is a diagram illustrating an example of a communication system according to an embodiment.
  • the communication system according to the embodiment includes, for example, a transmission device 100 and a reception device 10.
  • Transmitting apparatus 100 is a base station such as eNB (evolved Node B), for example.
  • the receiving device 10 is a terminal such as a UE (User Equipment).
  • the communication system according to the embodiment shown in FIG. 1 is an M ⁇ 1 MISO communication system in which the transmission apparatus 100 includes M transmission antennas 121 to 12M and the reception apparatus 10 includes one reception antenna 11. is there.
  • M is a natural number of 2 or more.
  • MISO is an abbreviation for Multi Input and Single Output (multiple input single output).
  • the transmission device 100 is a wireless transmission device including a transmitter 110 and M transmission antennas 121 to 12M.
  • the transmitter 110 is a generator (transmitter) that generates signals of M transmission slices 131 to 13M.
  • the transmitter 110 outputs the generated M signals to the transmission antennas 121 to 12M.
  • the transmission slices 131 to 13M will be described later (see, for example, FIG. 2).
  • the transmission antenna 121 wirelessly transmits the signal of the transmission slice 131 output from the transmitter 110.
  • the transmission antennas 122 to 12M wirelessly transmit the signals of the transmission slices 132 to 13M output from the transmitter 110, respectively.
  • the transmission antennas 121 to 12M are antennas arranged at equal intervals in an array.
  • the transmission antennas 121 and 122 are adjacent to each other, the transmission antennas 122 and 123 are adjacent to each other, and the transmission antennas 12 (M ⁇ 1) and 12M are adjacent to each other.
  • the receiving device 10 is a wireless receiving device including a receiving antenna 11 and a receiver 12.
  • the reception antenna 11 is a reception unit that receives each signal wirelessly transmitted from the transmission device 100. Then, the receiving antenna 11 outputs the received signal to the receiver 12.
  • the signal received by the receiving antenna 11 includes, for example, a transmission block 31 and noise 32.
  • the transmission block 31 is a combined signal of each signal of the transmission slices 131 to 13M, for example.
  • the noise 32 is noise generated by wireless transmission from the transmission device 100 to the reception device 10.
  • the receiver 12 is a decoding unit (receiver) that decodes each signal of the transmission slices 131 to 13M based on the signal output from the receiving antenna 11.
  • the receiver 12 performs decoding by MLD (Maximum Likelihood Detection).
  • MLD Maximum Likelihood Detection
  • decoding by the receiver 12 is not limited to MLD, and various decoding methods can be used.
  • the channel between the transmission device 100 and the reception device 10 is a channel with a slow fading and a flat frequency.
  • the channel responses of the transmitting antennas 121 to 12M can be simply expressed by complex-valued gain factors h 1 to h M , respectively.
  • the M ⁇ 1 MISO communication system in which the transmission apparatus 100 includes M transmission antennas 121 to 12M and the reception apparatus 10 includes one reception antenna 11 has been described.
  • the receiving device 10 may be configured to include a plurality of receiving antennas.
  • the transmission apparatus 100 is a base station such as eNB and the reception apparatus 10 is a terminal such as UE has been described, but the configuration is not limited thereto.
  • the transmission device 100 may be a terminal such as a UE.
  • the receiving device 10 may be a base station such as an eNB.
  • FIG. 2 is a diagram illustrating an example of a subcarrier, a transmission slice, and a transmission block according to the embodiment.
  • the horizontal direction indicates a time resource
  • the vertical direction indicates a frequency direction.
  • the minimum data transmission unit (radio resource unit) is a subcarrier.
  • transmission slice 131 includes 2 M ⁇ 1 subcarriers 201.
  • Data d 1,1 to d 1,2 ⁇ (M-1) are mapped to 2 M-1 subcarriers 201, respectively.
  • each of the 2 M-1 sub-carrier 201, one unit frequency resources, comprising 8 units frequency resources, is a rectangle of 1 ⁇ 8 in the time frequency plane in FIG.
  • the transmission slice 132 includes 2 M ⁇ 1 subcarriers 202.
  • the data d 2,1 to d 2,2 (M-1) are mapped to 2 M-1 subcarriers 202, respectively.
  • Each of the 2 M ⁇ 1 subcarriers 202 includes 2 units of frequency resources and 4 units of frequency resources, and is a 2 ⁇ 4 rectangle in the time-frequency plane of FIG.
  • the transmission slice 133 includes 2 M ⁇ 1 subcarriers 203.
  • the 2 M-1 sub-carrier 203, each of the data d 3,1 ⁇ d 3,2 ⁇ (M -1) is mapped.
  • Each of the 2 M-1 subcarriers 203 includes 4 units of frequency resources and 2 units of frequency resources, and is a 4 ⁇ 2 rectangle in the time-frequency plane of FIG.
  • transmission slice 13M includes 2 M-1 subcarriers 20M.
  • Data d M, 1 to d M, 2 ⁇ (M ⁇ 1) are mapped to 2 M ⁇ 1 subcarriers 20M, respectively.
  • Each of the 2 M-1 subcarriers 20M includes 8 units of frequency resources and 1 unit of frequency resources, and is an 8 ⁇ 1 rectangle in the time-frequency plane of FIG.
  • transmission slices 131 to 13M each include the same number (2 M-1 ) of subcarriers 201 to 20M. Further, the subcarriers 201 to 20M of the transmission slices 131 to 13M can have different rectangles on the time frequency plane in FIG. 2, but have the same area (time ⁇ frequency). Thereby, the data transmission performance of each subcarrier becomes the same.
  • the mth signal (1 ⁇ m ⁇ M) of the 1st to Mth signals has the time length in subcarrier m of the first signal. 2 m-1 times. Also, the m-th signal (1 ⁇ m ⁇ M) of the first to M-th signals has a bandwidth (frequency bandwidth) in the subcarrier that is 1/2 m ⁇ 1 of that of the first signal.
  • the transmission slices 131 to 13M are mapped to the transmission antennas 121 to 12M of the transmission apparatus 100 and simultaneously transmitted by radio as shown in FIG.
  • the channel between the transmission device 100 and the reception device 10 is a channel with a slow fading and a flat frequency.
  • each channel response in the time domain from time t 1 to time t 2 ⁇ (M-1) and each channel response in the frequency domain from frequency f 1 to frequency f 2 ⁇ (M-1) are the same. is there.
  • the channel response at the j th antenna at time t k and frequency f i can be simply represented by a complex gain factor h j (eg, h 1 to h M shown in FIG. 1).
  • LTE Long Term Evolution
  • OFDM Orthogonal Frequency Division Multiplexing (orthogonal frequency division multiplexing).
  • the OFDM subcarrier is a special conversion of wavelet conversion. That is, the waveform of the OFDM multicarrier is included in the multicarrier based on the wavelet.
  • FIG. 3 is a diagram illustrating an example of noise received by the receiving apparatus according to the embodiment.
  • the noise 32 that interferes with the transmission block 31 shown in FIG. 1 includes, for example, noise corresponding to each combination of time t 1 to t 2 ⁇ (M-1) and frequency f 1 to f 2 ⁇ (M-1). component ⁇ 1,1 ⁇ ⁇ 2 ⁇ (M -1), 2 ⁇ (M-1) are included.
  • the noise component ⁇ k, i at time t k and frequency f i satisfies, for example, the following expression (1).
  • k 1,2, ..., 2 (M-1)
  • i 1,2, ..., a 2 (M-1).
  • ⁇ 2 in the following equation (1) is noise energy received by each subcarrier.
  • the transmission apparatus 100 includes two transmission antennas 121 and 122, and wirelessly transmits the signals of the transmission slices 131 and 132 from the transmission antennas 121 and 122, respectively.
  • each data d 1, 1 is the transmission slice 131 includes two sub-carriers d 1, 2 is mapped.
  • the transmission slice 132 includes two subcarriers to which data d 2,1 and d 2,2 are mapped, respectively.
  • the reception signals received by the reception device 10 include, for example, reception signals r 1 to r 4 .
  • the received signal r 1 is a received component at time t 1 and frequencies f 1 and f 2 .
  • the received signal r 1, and the time t 1 and the frequency f 1, f 2 of the signal component 411, the time t 1 and the frequency f 1, f 2 of the noise 421, include.
  • the received signal r 2 is a received component at time t 2 and frequencies f 1 and f 2 .
  • Received signal r 3 is a received component at times t 1 and t 2 and frequency f 1 .
  • the received signal r 3, the time t 1, t 2 and the frequency f 1 of the signal component 413, the time t 1, t 2 and the frequency f 1 of the noise 423, include.
  • Received signal r 4 is a received component at times t 1 and t 2 and frequency f 2 .
  • the received signal r 4, and the time t 1, t 2 and the signal components 414 of the frequency f 2, and noise 424 of time t 1, t 2 and a frequency f 2, contains.
  • the received signals r 1 to r 4 can be expressed by the following equation (2), for example.
  • noise components eta k, i at time t k and the frequency f i satisfies, for example the following equation (3).
  • the receiving device 10 performs decoding using, for example, MLD.
  • the likelihood function in the AWGN channel can be expressed by, for example, the following equation (4) by minimizing the Euclidean distance.
  • AWGN is an abbreviation for Additive White Gaussian Noise (Additive White Gaussian Noise).
  • the receiving apparatus 10 decodes the data d 1,1 , d 1,2 , d 2,1 , d 2,2 by MLD based on, for example, h 1 and h 2 and the received signals r 1 to r 4. .
  • h 1, h 2 can be for example the reception apparatus 10 obtained by performing channel estimation based on the pilot signal from the transmitter 100.
  • the reception signals r 1 to r 4 can be obtained by filtering the data signal received by the reception device 10 from the transmission device 100 by time and frequency.
  • transmission apparatus 100 includes three transmission antennas 121 to 123, and wirelessly transmits signals of transmission slices 131 to 133 from transmission antennas 121 to 123, respectively. Therefore, the signal received by the receiving apparatus 10 includes the transmission block 31 in which the transmission slices 131 to 133 are synthesized and the noise 32.
  • the transmission slice 131 includes four subcarrier data d 1,1 ⁇ d 1,4 is mapped respectively.
  • Transmission slice 132 includes four subcarriers each mapped with data d 2,1 to d 2,4 .
  • Transmission slice 133 includes four subcarriers each mapped with data d 3,1 to d 3,4 .
  • the receiving apparatus 10 uses the data L 1,1 to d 1,4 , d 2,1 to d 2,4 , d 3,1 to d by MLD based on h 1 to h 3 and each received signal.
  • Decrypt 3,4 . h 1 to h 3 can be obtained, for example, when the receiving apparatus 10 performs channel estimation based on a pilot signal from the transmitting apparatus 100.
  • Each received signal can be obtained by filtering the data signal received from the transmitting apparatus 100 by the receiving apparatus 10 by time and frequency.
  • FIG. 6 is a diagram illustrating an example of the transmitter of the transmission apparatus according to the embodiment.
  • the transmitter 110 includes modulation channel encoding units 611 to 61M, inverse wavelet packet conversion units 621 to 62M (IWPT), and digital / analog conversion. And 631 to 63M (D / A).
  • IWPT is an abbreviation for inverse wavelet packet transform (inverse wavelet packet transform).
  • the modulation channel encoding units 611 to 61M and the inverse wavelet packet conversion units 621 to 62M can be realized by a digital processor such as an FPGA, DSP, or CPU, for example.
  • FPGA is an abbreviation for Field Programmable Gate Array.
  • DSP is an abbreviation for Digital Signal Processor.
  • CPU is an abbreviation for Central Processing Unit (Central Processing Unit).
  • the first data (DATA-1) is input to the modulation channel encoding unit 611.
  • Modulation channel coding section 611 performs channel coding of the input first data, and outputs a signal obtained by channel coding to inverse wavelet packet transform section 621.
  • the signal output from the modulation channel encoding unit 611 to the inverse wavelet packet conversion unit 621 is, for example, 2 M ⁇ 1 signals corresponding to the 2 M ⁇ 1 subcarriers 201 illustrated in FIG.
  • second to Mth data (DATA-2 to DATA-M) are input to modulation channel encoding sections 612 to 61M, respectively.
  • Modulation channel coding sections 612 to 61M perform channel coding of the input second to Mth data, respectively, and output signals obtained by channel coding to inverse wavelet packet transform sections 622 to 62M, respectively.
  • Inverse wavelet packet converters 621 to 62M perform inverse wavelet packet conversion based on different wavelet packets (WP-1 to WP-M) for the signals output from modulation channel encoders 611 to 61M, respectively. .
  • Signals of transmission slices 131 to 13M are obtained by inverse wavelet packet conversion by the inverse wavelet packet converters 621 to 62M, respectively.
  • the inverse wavelet packet transform units 621 to 62M perform inverse wavelet transform by repeating the operation of the orthogonal mirror filter a different number of times.
  • the inverse wavelet packet transform units 621 to 62M perform inverse wavelet transform by repeating the operation of the orthogonal mirror filter once to M times, respectively.
  • the signals of transmission slices 131 to 133 shown in FIG. 2 can be obtained.
  • the inverse wavelet packet converters 621 to 62M output the signals of the transmission slices 131 to 133 to the digital / analog converters 631 to 63M, respectively.
  • the digital / analog converter 631 converts the signal output from the inverse wavelet packet conversion unit 621 from a digital signal to an analog signal, and outputs the converted signal to the transmission antenna 121.
  • the digital / analog converters 632 to 63M convert the signals output from the inverse wavelet packet converters 622 to 62M from digital signals to analog signals, respectively, and output the converted signals to the transmission antennas 122 to 12M, respectively.
  • the signals output from the digital / analog converters 631 to 63M to the transmission antennas 121 to 12M are modulated and wirelessly transmitted from the transmission antennas 121 to 12M.
  • the transmission signal in the discrete domain is composed of continuous modulation symbols that are the sum of 2 M-1 waveforms after channel coding and by inverse wavelet packet transformation based on different wavelet packets. Is done. That is, the kth data (DATA-k) is manipulated by the IWPT based on the kth wavelet packet.
  • FIG. 7 is a diagram illustrating an example of a receiver of the receiving apparatus according to the embodiment.
  • the receiver 12 includes an analog / digital converter 710 (A / D), wavelet packet converters 721 to 72M (WPT), and an MLD decoder. 730.
  • WPT is an abbreviation for Wavelet Packet Transform.
  • the wavelet packet conversion units 721 to 72M and the MLD decoding unit 730 can be realized by a digital processor such as an FPGA, a DSP, or a CPU.
  • Analog / digital converter 710 converts the signal output from reception antenna 11 from an analog signal to a digital signal, and outputs the converted signal to wavelet packet conversion units 721 to 72M.
  • the signal output from the analog / digital converter 710 to the wavelet packet converters 721 to 72M includes the transmission block 31 and noise 32 (for example, AWGN noise).
  • the wavelet packet conversion units 721 to 72M perform wavelet packet conversion (WPT) based on different wavelet packets (WP-1 to WP-M) on the signal output from the analog / digital converter 710.
  • the wavelet packets (WP-1 to WP-M) used by the wavelet packet conversion units 721 to 72M are wavelet packets corresponding to the wavelet packets used by the inverse wavelet packet conversion units 621 to 62M (see FIG. 6), respectively.
  • Each of the wavelet packet conversion units 721 to 72M outputs a signal (subcarrier waveform) obtained by the wavelet packet conversion to the MLD decoding unit 730.
  • the MLD decoding unit 730 obtains the decoding results DATA-1 ′ to DATA-M ′ of the first to Mth data by MLD based on the signals output from the wavelet packet conversion units 721 to 72M. Further, the MLD decoding unit 730 outputs the obtained decoding results DATA-1 ′ to DATA-M ′.
  • Wavelet packet The wavelet packet will be described.
  • discrete wavelet packet conversion can be used for wavelet conversion in the above-described inverse wavelet packet conversion units 621 to 62M and wavelet packet conversion units 721 to 72M.
  • a pair of wavelet filters h [n] and g [n] belong to a high-pass filter and a low-pass filter each having a quadrature mirror filter characteristic.
  • the relationship between h [n] and g [n] is expressed by the following equation (5), for example.
  • DWPT discrete wavelet packet transform
  • a signal is constructed as the sum of 2 j waveforms. These waveforms can be constructed by j successive iterations, each consisting of filtering and upsampling. Accordingly, the discrete wavelet packet transform can be defined as a set of recursive functions, for example, as shown in the following equation (6).
  • FIG. 8 is a diagram illustrating an example of a relationship between the SNR and the symbol error rate according to the embodiment.
  • the horizontal axis indicates the SNR
  • the vertical axis indicates the symbol error rate.
  • SNR is an abbreviation for Signal to Noise Ratio (signal to noise ratio).
  • FIG. 8 shows an example in which QPSK modulation is used as the modulation method.
  • QPSK is an abbreviation for Quadrature Phase Shift Keying.
  • the SNR symbol error rate characteristic 801 indicates the characteristic of the symbol error rate with respect to the SNR in the 2 ⁇ 1 MISO communication system (for example, see FIG. 4) according to the embodiment.
  • the SNR symbol error rate characteristic 802 shows the symbol error rate characteristic with respect to the SNR in a 2 ⁇ 1 MISO communication system that performs precoding by feeding back CSI.
  • An SNR symbol error rate characteristic 803 indicates a symbol error rate characteristic with respect to an SNR in a 1 ⁇ 1 SISO communication system that performs precoding by feeding back CSI.
  • SISO is an abbreviation for Single Input and Single Output (single input single output).
  • FIG. 9 is a diagram illustrating another example of the relationship between the SNR and the symbol error rate according to the embodiment.
  • the horizontal axis indicates the SNR
  • the vertical axis indicates the symbol error rate.
  • FIG. 9 shows an example in which 16QAM modulation is used as the modulation method.
  • QAM is an abbreviation for Quadrature Amplitude Modulation.
  • the SNR symbol error rate characteristic 901 indicates the symbol error rate characteristic with respect to the SNR in the 2 ⁇ 1 MISO communication system (see FIG. 4 for example) according to the embodiment.
  • An SNR symbol error rate characteristic 902 shows a symbol error rate characteristic with respect to SNR in a 2 ⁇ 1 MISO communication system that performs precoding by feeding back CSI.
  • An SNR symbol error rate characteristic 903 indicates a symbol error rate characteristic with respect to an SNR in a 1 ⁇ 1 SISO communication system that performs precoding by feeding back CSI.
  • FIG. 10 is a diagram illustrating still another example of the relationship between the SNR and the symbol error rate according to the embodiment.
  • the horizontal axis indicates the SNR
  • the vertical axis indicates the symbol error rate.
  • FIG. 10 shows an example in which QPSK modulation is used as the modulation method.
  • the SNR symbol error rate characteristic 1001 indicates the characteristic of the symbol error rate with respect to the SNR in the 3 ⁇ 1 MISO communication system (see, for example, FIG. 5) according to the embodiment.
  • An SNR symbol error rate characteristic 1002 shows a symbol error rate characteristic with respect to an SNR in a 3 ⁇ 1 MISO communication system that performs precoding by feeding back CSI.
  • An SNR symbol error rate characteristic 1003 shows a symbol error rate characteristic with respect to an SNR in a 1 ⁇ 1 SISO communication system that performs precoding by feeding back CSI.
  • the MISO communication system according to the embodiment can achieve performance close to the best case of the 1 ⁇ 1 SISO communication system, for example, when the transmission power from each transmission antenna is the same. . Therefore, the MISO communication system according to the embodiment can achieve the same capacity as MISO that performs feedback such as CSI without performing feedback such as CSI.
  • the MISO communication system according to the embodiment can obtain particularly high performance when QPSK modulation is used as a modulation method.
  • the time and frequency size associated with modulation increase, and thus the gain increases.
  • a plurality of signals having the same product of time length and bandwidth and different combinations of time length and bandwidth in the radio resource unit (subcarrier) to which data is allocated are reversed. It can be generated by wavelet transform. A plurality of generated signals can be transmitted from a plurality of antennas. Thereby, transmission quality (for example, error rate) can be improved without transmitting a feedback signal such as CSI from the receiving apparatus 10 to the transmitting apparatus 100, for example.
  • transmission quality for example, error rate
  • transmission quality can be improved without feedback of channel state information.
  • MIMO multiple Input Multiple Output
  • IEEE is an abbreviation for the Institute of Electrical and Electronics Engineers.
  • the linear precoding MIMO scheme is implemented by, for example, ZF, MMSE or SVD when there is sufficient fieldback due to CSI.
  • ZF is an abbreviation for Zero Forcing.
  • MMSE is an abbreviation for Minimum Mean Square Error (least square error method).
  • SVD is an abbreviation for Single Value Decomposition.
  • high capacity gain can be realized without performing CSI feedback by efficient transmission considering frequency and time modulation transmission based on wavelet space.
  • the transmission method and the reception method described in this embodiment can be realized by executing a program prepared in advance on a computer of a communication apparatus.
  • This program is recorded on a computer-readable recording medium such as a hard disk, a flexible disk, a CD-ROM, and a DVD, and is executed by being read from the recording medium by the computer.
  • CD-ROM is an abbreviation for Compact Disc-Read Only Memory.
  • DVD is an abbreviation for Digital Versatile Disc.
  • the program may be a transmission medium that can be distributed via a network such as the Internet.

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Abstract

A transmission apparatus (100) is provided with a transmitter (110) and transmission antennas (121-12M). The transmitter (110) generates, by means of inverse wavelet transformation, a plurality of signals each having the same product of the time length and the bandwidth in a radio resource unit, to which data is allocated, and also having a respective different combination of the time length and the bandwidth in the radio resource unit. The transmission antennas (121-12M) transmit the respective ones of the plurality of signals generated by the transmitter (110).

Description

基地局、端末、送信プログラム、受信プログラム、送信方法および受信方法Base station, terminal, transmission program, reception program, transmission method and reception method
　本発明は、基地局、端末、送信プログラム、受信プログラム、送信方法および受信方法に関する。 The present invention relates to a base station, a terminal, a transmission program, a reception program, a transmission method, and a reception method.
　従来、複数の送信アンテナを用いて無線信号を伝送する場合に、受信側から送信されるＣＳＩ等のフィードバック情報に基づいて送信側がプリコーディングを行い伝送品質を向上させる技術が知られている。ＣＳＩはＣｈａｎｎｅｌ　Ｓｔａｔｅ　Ｉｎｆｏｒｍａｔｉｏｎ（チャネル状態情報）の略である。また、ウェーブレット変換を用いてマルチアンテナ向けのチャネルを生成する技術が知られている（たとえば、下記特許文献１～３参照。）。 Conventionally, when transmitting a radio signal using a plurality of transmission antennas, a technique for improving transmission quality by performing precoding on the transmission side based on feedback information such as CSI transmitted from the reception side is known. CSI is an abbreviation for Channel State Information. A technique for generating a channel for a multi-antenna using wavelet transform is known (see, for example, Patent Documents 1 to 3 below).
国際公開第２００６／１０６６９３号International Publication No. 2006/106693 特表２００７－５２４３１９号公報Special table 2007-524319 国際公開第２０１２／０７７２９９号International Publication No. 2012/077299
　しかしながら、上述した従来技術では、チャネル状態情報等のフィードバックに多くのオーバーヘッドを要するという問題がある。 However, the above-described conventional technique has a problem that a lot of overhead is required for feedback of channel state information and the like.
　１つの側面では、本発明は、チャネル状態情報のフィードバックがなくても伝送品質の向上を図ることができる基地局、端末、送信プログラム、受信プログラム、送信方法および受信方法を提供することを目的とする。 In one aspect, an object of the present invention is to provide a base station, a terminal, a transmission program, a reception program, a transmission method, and a reception method that can improve transmission quality without feedback of channel state information. To do.
　上述した課題を解決し、目的を達成するため、１つの実施態様では、データを割り当てる無線リソース単位における時間長と帯域幅との積が互いに同じであり、かつ前記無線リソース単位における時間長と帯域幅との組み合わせが互いに異なる複数の信号を逆ウェーブレット変換により生成する生成部と、前記生成部によって生成された前記複数の信号をそれぞれ送信する複数のアンテナと、を備える基地局、送信プログラムおよび送信方法が提案される。 In order to solve the above-described problems and achieve the object, in one embodiment, the product of the time length and the bandwidth in the radio resource unit to which data is allocated is the same, and the time length and the bandwidth in the radio resource unit A base station, a transmission program, and a transmission comprising: a generation unit that generates a plurality of signals with different combinations of widths by inverse wavelet transform; and a plurality of antennas that respectively transmit the plurality of signals generated by the generation unit A method is proposed.
　また、別の１つの実施態様では、データを割り当てる無線リソース単位における時間長と帯域幅との積が互いに同じであり、かつ前記無線リソース単位における時間長と帯域幅との組み合わせが互いに異なる複数の信号を逆ウェーブレット変換により生成し、生成した前記複数の信号をそれぞれ複数のアンテナにより送信する基地局から前記複数の信号を受信する受信部と、前記受信部によって受信された信号を復号する復号部と、を備える端末、受信プログラムおよび受信方法が提案される。 In another embodiment, the product of the time length and the bandwidth in the radio resource unit to which the data is allocated is the same, and the combination of the time length and the bandwidth in the radio resource unit is different from each other. A receiving unit that generates a signal by inverse wavelet transform, receives the plurality of signals from a base station that transmits the generated plurality of signals by a plurality of antennas, and a decoding unit that decodes the signals received by the receiving unit A terminal, a receiving program, and a receiving method are proposed.
　１つの側面では、本発明は、チャネル状態情報のフィードバックがなくても伝送品質の向上を図ることができるという効果を奏する。 In one aspect, the present invention has an effect that transmission quality can be improved without feedback of channel state information.
図１は、実施の形態にかかる通信システムの一例を示す図である。FIG. 1 is a diagram illustrating an example of a communication system according to an embodiment. 図２は、実施の形態にかかるサブキャリア、トランスミッションスライスおよびトランスミッションブロックの一例を示す図である。FIG. 2 is a diagram illustrating an example of a subcarrier, a transmission slice, and a transmission block according to the embodiment. 図３は、実施の形態にかかる受信装置が受信するノイズの一例を示す図である。FIG. 3 is a diagram illustrating an example of noise received by the receiving apparatus according to the embodiment. 図４は、実施の形態にかかる送信装置（Ｍ＝２）によるウェーブレットパケット変調のチャネルの一例を示す図である。FIG. 4 is a diagram illustrating an example of a wavelet packet modulation channel by the transmission apparatus (M = 2) according to the embodiment. 図５は、実施の形態にかかる送信装置（Ｍ＝３）によるウェーブレットパケット変調のチャネルの一例を示す図である。FIG. 5 is a diagram illustrating an example of a wavelet packet modulation channel by the transmission apparatus (M = 3) according to the embodiment. 図６は、実施の形態にかかる送信装置の送信機の一例を示す図である。FIG. 6 is a diagram illustrating an example of the transmitter of the transmission apparatus according to the embodiment. 図７は、実施の形態にかかる受信装置の受信機の一例を示す図である。FIG. 7 is a diagram illustrating an example of a receiver of the receiving apparatus according to the embodiment. 図８は、実施の形態にかかるＳＮＲとシンボルエラーレートとの間の関係の一例を示す図である。FIG. 8 is a diagram illustrating an example of a relationship between the SNR and the symbol error rate according to the embodiment. 図９は、実施の形態にかかるＳＮＲとシンボルエラーレートとの間の関係の他の一例を示す図である。FIG. 9 is a diagram illustrating another example of the relationship between the SNR and the symbol error rate according to the embodiment. 図１０は、実施の形態にかかるＳＮＲとシンボルエラーレートとの間の関係のさらに他の一例を示す図である。FIG. 10 is a diagram illustrating still another example of the relationship between the SNR and the symbol error rate according to the embodiment.
　以下に図面を参照して、本発明にかかる基地局、端末、送信プログラム、受信プログラム、送信方法および受信方法の実施の形態を詳細に説明する。 Embodiments of a base station, a terminal, a transmission program, a reception program, a transmission method, and a reception method according to the present invention will be described in detail below with reference to the drawings.
（実施の形態）
（実施の形態にかかる通信システム）
　図１は、実施の形態にかかる通信システムの一例を示す図である。図１に示すように、実施の形態にかかる通信システムは、たとえば、送信装置１００と、受信装置１０と、を含む。送信装置１００は、たとえばｅＮＢ（ｅｖｏｌｖｅｄ　Ｎｏｄｅ　Ｂ）などの基地局である。受信装置１０は、たとえばＵＥ（Ｕｓｅｒ　Ｅｑｕｉｐｍｅｎｔ：ユーザ端末）などの端末である。 (Embodiment)
(Communication system according to embodiment)
FIG. 1 is a diagram illustrating an example of a communication system according to an embodiment. As illustrated in FIG. 1, the communication system according to the embodiment includes, for example, a transmission device 100 and a reception device 10. Transmitting apparatus 100 is a base station such as eNB (evolved Node B), for example. The receiving device 10 is a terminal such as a UE (User Equipment).
　また、図１に示す実施の形態にかかる通信システムは、送信装置１００がＭ本の送信アンテナ１２１～１２Ｍを備え、受信装置１０が１本の受信アンテナ１１を備えるＭ×１のＭＩＳＯ通信システムである。Ｍは２以上の自然数である。ＭＩＳＯはＭｕｌｔｉ　Ｉｎｐｕｔ　ａｎｄ　Ｓｉｎｇｌｅ　Ｏｕｔｐｕｔ（複数入力単一出力）の略である。 The communication system according to the embodiment shown in FIG. 1 is an M × 1 MISO communication system in which the transmission apparatus 100 includes M transmission antennas 121 to 12M and the reception apparatus 10 includes one reception antenna 11. is there. M is a natural number of 2 or more. MISO is an abbreviation for Multi Input and Single Output (multiple input single output).
　送信装置１００は、送信機１１０と、Ｍ本の送信アンテナ１２１～１２Ｍと、を備える無線送信装置である。送信機１１０は、Ｍ通りのトランスミッションスライス１３１～１３Ｍの各信号を生成する生成部（トランスミッタ）である。送信機１１０は、生成したＭ個の各信号をそれぞれ送信アンテナ１２１～１２Ｍへ出力する。トランスミッションスライス１３１～１３Ｍについては後述する（たとえば図２参照）。 The transmission device 100 is a wireless transmission device including a transmitter 110 and M transmission antennas 121 to 12M. The transmitter 110 is a generator (transmitter) that generates signals of M transmission slices 131 to 13M. The transmitter 110 outputs the generated M signals to the transmission antennas 121 to 12M. The transmission slices 131 to 13M will be described later (see, for example, FIG. 2).
　送信アンテナ１２１は、送信機１１０から出力されたトランスミッションスライス１３１の信号を無線送信する。同様に、送信アンテナ１２２～１２Ｍは、それぞれ送信機１１０から出力されたトランスミッションスライス１３２～１３Ｍの各信号を無線送信する。 The transmission antenna 121 wirelessly transmits the signal of the transmission slice 131 output from the transmitter 110. Similarly, the transmission antennas 122 to 12M wirelessly transmit the signals of the transmission slices 132 to 13M output from the transmitter 110, respectively.
　たとえば、送信アンテナ１２１～１２Ｍは、アレイ状に等間隔に配置された各アンテナである。そして、送信アンテナ１２１，１２２が互いに隣接し、送信アンテナ１２２，１２３が互いに隣接し、…送信アンテナ１２（Ｍ－１），１２Ｍが互いに隣接している。 For example, the transmission antennas 121 to 12M are antennas arranged at equal intervals in an array. The transmission antennas 121 and 122 are adjacent to each other, the transmission antennas 122 and 123 are adjacent to each other, and the transmission antennas 12 (M−1) and 12M are adjacent to each other.
　受信装置１０は、受信アンテナ１１と、受信機１２と、を備える無線受信装置である。受信アンテナ１１は、送信装置１００から無線送信された各信号を受信する受信部である。そして、受信アンテナ１１は、受信した信号を受信機１２へ出力する。受信アンテナ１１が受信する信号には、たとえばトランスミッションブロック３１およびノイズ３２が含まれる。トランスミッションブロック３１は、たとえばトランスミッションスライス１３１～１３Ｍの各信号の合成信号である。ノイズ３２は、送信装置１００から受信装置１０への無線伝送で発生したノイズである。 The receiving device 10 is a wireless receiving device including a receiving antenna 11 and a receiver 12. The reception antenna 11 is a reception unit that receives each signal wirelessly transmitted from the transmission device 100. Then, the receiving antenna 11 outputs the received signal to the receiver 12. The signal received by the receiving antenna 11 includes, for example, a transmission block 31 and noise 32. The transmission block 31 is a combined signal of each signal of the transmission slices 131 to 13M, for example. The noise 32 is noise generated by wireless transmission from the transmission device 100 to the reception device 10.
　受信機１２は、受信アンテナ１１から出力された信号に基づいて、トランスミッションスライス１３１～１３Ｍの各信号を復号する復号部（レシーバ）である。たとえば、受信機１２は、ＭＬＤ（Ｍａｘｉｍｕｍ　Ｌｉｋｅｌｉｈｏｏｄ　Ｄｅｔｅｃｔｉｏｎ：最尤検出）による復号を行う。ただし、受信機１２による復号には、ＭＬＤに限らず各種の方式の復号方式を用いることができる。 The receiver 12 is a decoding unit (receiver) that decodes each signal of the transmission slices 131 to 13M based on the signal output from the receiving antenna 11. For example, the receiver 12 performs decoding by MLD (Maximum Likelihood Detection). However, decoding by the receiver 12 is not limited to MLD, and various decoding methods can be used.
　ここで、送信装置１００と受信装置１０との間のチャネルが、フェージングが遅く周波数がフラットなチャネルであるとする。この場合に、後述のように、送信アンテナ１２１～１２Ｍの各チャネル応答はそれぞれ複素数利得係数（ｃｏｍｐｌｅｘ－ｖａｌｕｅｄ　ｇａｉｎ　ｆａｃｔｏｒ）のｈ1～ｈMによって単純に表すことができる。 Here, it is assumed that the channel between the transmission device 100 and the reception device 10 is a channel with a slow fading and a flat frequency. In this case, as will be described later, the channel responses of the transmitting antennas 121 to 12M can be simply expressed by complex-valued gain factors h 1 to h M , respectively.
　図１に示す例では、送信装置１００がＭ本の送信アンテナ１２１～１２Ｍを備え、受信装置１０が１本の受信アンテナ１１を備えるＭ×１のＭＩＳＯ通信システムについて説明したが、このような構成に限らない。たとえば、受信装置１０は、複数の受信アンテナを備える構成としてもよい。 In the example illustrated in FIG. 1, the M × 1 MISO communication system in which the transmission apparatus 100 includes M transmission antennas 121 to 12M and the reception apparatus 10 includes one reception antenna 11 has been described. Not limited to. For example, the receiving device 10 may be configured to include a plurality of receiving antennas.
　また、一例として、送信装置１００がｅＮＢなどの基地局であり、受信装置１０がＵＥなどの端末である場合について説明したが、このような構成に限らない。たとえば、送信装置１００がＵＥなどの端末であってもよい。また、受信装置１０がｅＮＢなどの基地局であってもよい。 Further, as an example, the case where the transmission apparatus 100 is a base station such as eNB and the reception apparatus 10 is a terminal such as UE has been described, but the configuration is not limited thereto. For example, the transmission device 100 may be a terminal such as a UE. Further, the receiving device 10 may be a base station such as an eNB.
（実施の形態にかかるサブキャリア、トランスミッションスライスおよびトランスミッションブロック）
　図２は、実施の形態にかかるサブキャリア、トランスミッションスライスおよびトランスミッションブロックの一例を示す図である。図２に示すトランスミッションスライス１３１～１３Ｍのそれぞれにおいて、横方向は時間リソースを示し、縦方向は周波数方向を示す。ここで、データの最小送信単位（無線リソース単位）をサブキャリアとする。 (Subcarrier, transmission slice and transmission block according to the embodiment)
FIG. 2 is a diagram illustrating an example of a subcarrier, a transmission slice, and a transmission block according to the embodiment. In each of the transmission slices 131 to 13M shown in FIG. 2, the horizontal direction indicates a time resource, and the vertical direction indicates a frequency direction. Here, the minimum data transmission unit (radio resource unit) is a subcarrier.
　たとえばトランスミッションスライス１３１は２M-1個のサブキャリア２０１を含む。２M-1個のサブキャリア２０１には、それぞれデータｄ1,1～ｄ1,2^(M-1)がマッピングされる。また、２M-1個のサブキャリア２０１のそれぞれは、周波数リソースを１単位、周波数リソースを８単位含み、図２の時間周波数平面において１×８の長方形である。 For example, transmission slice 131 includes 2 M−1 subcarriers 201. Data d 1,1 to d 1,2 ^ (M-1) are mapped to 2 M-1 subcarriers 201, respectively. Further, each of the 2 M-1 sub-carrier 201, one unit frequency resources, comprising 8 units frequency resources, is a rectangle of 1 × 8 in the time frequency plane in FIG.
　また、トランスミッションスライス１３２は２M-1個のサブキャリア２０２を含む。２M-1個のサブキャリア２０２には、それぞれデータｄ2,1～ｄ2,2^(M-1)がマッピングされる。また、２M-1個のサブキャリア２０２のそれぞれは、周波数リソースを２単位、周波数リソースを４単位含み、図２の時間周波数平面において２×４の長方形である。 The transmission slice 132 includes 2 M−1 subcarriers 202. The data d 2,1 to d 2,2 (M-1) are mapped to 2 M-1 subcarriers 202, respectively. Each of the 2 M−1 subcarriers 202 includes 2 units of frequency resources and 4 units of frequency resources, and is a 2 × 4 rectangle in the time-frequency plane of FIG.
　また、図２においては図示を省略しているが、トランスミッションスライス１３３は２M-1個のサブキャリア２０３を含む。２M-1個のサブキャリア２０３には、それぞれデータｄ3,1～ｄ3,2^(M-1)がマッピングされる。また、２M-1個のサブキャリア２０３のそれぞれは、周波数リソースを４単位、周波数リソースを２単位含み、図２の時間周波数平面において４×２の長方形である。 Although not shown in FIG. 2, the transmission slice 133 includes 2 M−1 subcarriers 203. The 2 M-1 sub-carrier 203, each of the data d 3,1 ~ d 3,2 ^ (M -1) is mapped. Each of the 2 M-1 subcarriers 203 includes 4 units of frequency resources and 2 units of frequency resources, and is a 4 × 2 rectangle in the time-frequency plane of FIG.
　同様に、トランスミッションスライス１３Ｍは２M-1個のサブキャリア２０Ｍを含む。２M-1個のサブキャリア２０Ｍには、それぞれデータｄM,1～ｄM,2^(M-1)がマッピングされる。また、２M-1個のサブキャリア２０Ｍのそれぞれは、周波数リソースを８単位、周波数リソースを１単位含み、図２の時間周波数平面において８×１の長方形である。 Similarly, transmission slice 13M includes 2 M-1 subcarriers 20M. Data d M, 1 to d M, 2 ^ (M−1) are mapped to 2 M−1 subcarriers 20M, respectively. Each of the 2 M-1 subcarriers 20M includes 8 units of frequency resources and 1 unit of frequency resources, and is an 8 × 1 rectangle in the time-frequency plane of FIG.
　図２に示したように、トランスミッションスライス１３１～１３Ｍは、それぞれ同数（２M-1個）のサブキャリア２０１～２０Ｍを含む。また、トランスミッションスライス１３１～１３Ｍのサブキャリア２０１～２０Ｍは、図２の時間周波数平面において、互いに異なる長方形となり得るが、互いに同じ面積（時間×周波数）を有する。これにより、各サブキャリアのデータ伝送性能は同じになる。 As shown in FIG. 2, transmission slices 131 to 13M each include the same number (2 M-1 ) of subcarriers 201 to 20M. Further, the subcarriers 201 to 20M of the transmission slices 131 to 13M can have different rectangles on the time frequency plane in FIG. 2, but have the same area (time × frequency). Thereby, the data transmission performance of each subcarrier becomes the same.
　トランスミッションスライス１３１～１３Ｍの各信号を第１～第Ｍ信号とすると、第１～第Ｍ信号のうちの第ｍ信号（１≦ｍ≦Ｍ）は、サブキャリアｍにおける時間長が第１信号の２m-1倍になる。また、第１～第Ｍ信号のうちの第ｍ信号（１≦ｍ≦Ｍ）は、サブキャリアにおける帯域幅（周波数帯域幅）が第１信号の２m-1分の１になる。 Assuming that the signals of transmission slices 131 to 13M are the 1st to Mth signals, the mth signal (1 ≦ m ≦ M) of the 1st to Mth signals has the time length in subcarrier m of the first signal. 2 m-1 times. Also, the m-th signal (1 ≦ m ≦ M) of the first to M-th signals has a bandwidth (frequency bandwidth) in the subcarrier that is 1/2 m−1 of that of the first signal.
　たとえば、第２信号（トランスミッションスライス１３２の信号）は、サブキャリアにおける時間長が第１信号の２2-1＝２倍であり、サブキャリアにおける帯域幅が第１信号の２2-1分の１＝２分の１（半分）である。また、第３信号（トランスミッションスライス１３３の信号）は、サブキャリアにおける時間長が第１信号の２3-1＝４倍であり、サブキャリアにおける帯域幅が第１信号の２3-1分の１＝４分の１である。 For example, the second signal (the signal of transmission slice 132) has a time length in the subcarrier of 2 2-1 = 2 times that of the first signal, and the bandwidth in the subcarrier is 2 2-1 minutes of the first signal. 1 = 1/2 (half). The third signal (the signal of transmission slice 133) has a time length in the subcarrier of 2 3-1 = 4 times that of the first signal, and the bandwidth in the subcarrier is 2 3-1 minutes of that of the first signal. 1 = 1/4.
　また、トランスミッションスライス１３１～１３Ｍは、図１に示したようにそれぞれ送信装置１００の送信アンテナ１２１～１２Ｍにマッピングされて同時に無線送信されることにより、トランスミッションブロック３１として受信装置１０へ送信される。 Further, the transmission slices 131 to 13M are mapped to the transmission antennas 121 to 12M of the transmission apparatus 100 and simultaneously transmitted by radio as shown in FIG.
　たとえば、送信装置１００と受信装置１０との間のチャネルが、フェージングが遅く周波数がフラットなチャネルであるとする。この場合に、時間ｔ1から時間ｔ2^(M-1)までの時間領域における各チャネル応答および周波数ｆ1から周波数ｆ2^(M-1)までの周波数領域における各チャネル応答は同じである。これは、時間ｔkおよび周波数ｆiにおけるｊ番目のアンテナにおけるチャネル応答が、複素数利得係数ｈj（たとえば図１に示したｈ1～ｈM）によって単純に表すことができることを意味する。 For example, it is assumed that the channel between the transmission device 100 and the reception device 10 is a channel with a slow fading and a flat frequency. In this case, each channel response in the time domain from time t 1 to time t 2 ^ (M-1) and each channel response in the frequency domain from frequency f 1 to frequency f 2 ^ (M-1) are the same. is there. This means that the channel response at the j th antenna at time t k and frequency f i can be simply represented by a complex gain factor h j (eg, h 1 to h M shown in FIG. 1).
　たとえばＬＴＥのＯＦＤＭシステムにおいては、このようなチャネルは、７．５［ｋＨｚ］、１５［ｋＨｚ］、３０［ｋＨｚ］、６０［ｋＨｚ］および１２０［ｋＨｚ］などのサブキャリア空間によって容易に生成することができる。また、サブキャリア間隔はそれぞれ１６Ｔc，８Ｔc，４Ｔc，２Ｔc，Ｔcとなる。ＬＴＥはＬｏｎｇ　Ｔｅｒｍ　Ｅｖｏｌｕｔｉｏｎの略である。ＯＦＤＭはＯｒｔｈｏｇｏｎａｌ　Ｆｒｅｑｕｅｎｃｙ　Ｄｉｖｉｓｉｏｎ　Ｍｕｌｔｉｐｌｅｘｉｎｇ（直交周波数分割多重）の略である。なおＯＦＤＭサブキャリアはウェーブレット変換の特殊な変換である。すなわち、ＯＦＤＭマルチキャリアの波形は、ウェーブレットをベースとしたマルチキャリアに含まれる。 For example, in the LTE OFDM system, such a channel is easily generated by subcarrier spaces such as 7.5 [kHz], 15 [kHz], 30 [kHz], 60 [kHz] and 120 [kHz]. be able to. Further, each sub-carrier spacing 16T c, 8T c, 4T c , 2T c, the T c. LTE is an abbreviation for Long Term Evolution. OFDM is an abbreviation for Orthogonal Frequency Division Multiplexing (orthogonal frequency division multiplexing). The OFDM subcarrier is a special conversion of wavelet conversion. That is, the waveform of the OFDM multicarrier is included in the multicarrier based on the wavelet.
（実施の形態にかかる受信装置が受信するノイズ）
　図３は、実施の形態にかかる受信装置が受信するノイズの一例を示す図である。図１に示したトランスミッションブロック３１に干渉するノイズ３２には、たとえば、時間ｔ1～ｔ2^(M-1)および周波数ｆ1～ｆ2^(M-1)の各組み合わせに対応するノイズ成分η1,1～η2^(M-1),2^(M-1)が含まれる。 (Noise received by receiving apparatus according to embodiment)
FIG. 3 is a diagram illustrating an example of noise received by the receiving apparatus according to the embodiment. The noise 32 that interferes with the transmission block 31 shown in FIG. 1 includes, for example, noise corresponding to each combination of time t 1 to t 2 ^ (M-1) and frequency f 1 to f 2 ^ (M-1). component η 1,1 ~ η 2 ^ (M -1), 2 ^ (M-1) are included.
　時間ｔkおよび周波数ｆiにおけるノイズ成分ηk,iは、たとえば下記（１）式を満たす。なお、ｋ＝１，２，…，２(M-1)、ｉ＝１，２，…，２(M-1)である。下記（１）式のδ2は各サブキャリアで受信されるノイズエネルギーである。 The noise component η k, i at time t k and frequency f i satisfies, for example, the following expression (1). Note, k = 1,2, ..., 2 (M-1), i = 1,2, ..., a 2 (M-1). Δ 2 in the following equation (1) is noise energy received by each subcarrier.
Figure JPOXMLDOC01-appb-M000001
Figure JPOXMLDOC01-appb-M000001
（実施の形態にかかる送信装置（Ｍ＝２）によるウェーブレットパケット変調のチャネル）
　図４は、実施の形態にかかる送信装置（Ｍ＝２）によるウェーブレットパケット変調のチャネルの一例を示す図である。図４においては、一例として２×１のＭＩＳＯ通信システム（Ｍ＝２）について説明する。この場合に、送信装置１００は、２本の送信アンテナ１２１，１２２を備え、送信アンテナ１２１，１２２からそれぞれトランスミッションスライス１３１，１３２の信号を無線送信する。 (Channel of Wavelet Packet Modulation by Transmitter (M = 2) According to Embodiment)
FIG. 4 is a diagram illustrating an example of a wavelet packet modulation channel by the transmission apparatus (M = 2) according to the embodiment. In FIG. 4, a 2 × 1 MISO communication system (M = 2) will be described as an example. In this case, the transmission apparatus 100 includes two transmission antennas 121 and 122, and wirelessly transmits the signals of the transmission slices 131 and 132 from the transmission antennas 121 and 122, respectively.
　この場合に、トランスミッションスライス１３１にはそれぞれデータｄ1,1，ｄ1,2がマッピングされた２つのサブキャリアが含まれる。トランスミッションスライス１３２にはそれぞれデータｄ2,1，ｄ2,2がマッピングされた２つのサブキャリアが含まれる。 In this case, each data d 1, 1 is the transmission slice 131 includes two sub-carriers d 1, 2 is mapped. The transmission slice 132 includes two subcarriers to which data d 2,1 and d 2,2 are mapped, respectively.
　受信装置１０が受信する受信信号には、たとえば受信信号ｒ1～ｒ4が含まれる。受信信号ｒ1は、時間ｔ1および周波数ｆ1，ｆ2の受信成分である。受信信号ｒ1には、時間ｔ1および周波数ｆ1，ｆ2の信号成分４１１と、時間ｔ1および周波数ｆ1，ｆ2のノイズ４２１と、が含まれる。 The reception signals received by the reception device 10 include, for example, reception signals r 1 to r 4 . The received signal r 1 is a received component at time t 1 and frequencies f 1 and f 2 . The received signal r 1, and the time t 1 and the frequency f 1, f 2 of the signal component 411, the time t 1 and the frequency f 1, f 2 of the noise 421, include.
　受信信号ｒ2は、時間ｔ2および周波数ｆ1，ｆ2の受信成分である。受信信号ｒ2には、時間ｔ2および周波数ｆ1，ｆ2の信号成分４１２と、時間ｔ2および周波数ｆ1，ｆ2のノイズ４２２と、が含まれる。受信信号ｒ3は、時間ｔ1，ｔ2および周波数ｆ1の受信成分である。受信信号ｒ3には、時間ｔ1，ｔ2および周波数ｆ1の信号成分４１３と、時間ｔ1，ｔ2および周波数ｆ1のノイズ４２３と、が含まれる。 The received signal r 2 is a received component at time t 2 and frequencies f 1 and f 2 . The received signal r 2, and the time t 2 and a frequency f 1, f 2 of the signal component 412, and the time t 2 and a frequency f 1, f 2 of the noise 422, include. Received signal r 3 is a received component at times t 1 and t 2 and frequency f 1 . The received signal r 3, the time t 1, t 2 and the frequency f 1 of the signal component 413, the time t 1, t 2 and the frequency f 1 of the noise 423, include.
　受信信号ｒ4は、時間ｔ1，ｔ2および周波数ｆ2の受信成分である。受信信号ｒ4には、時間ｔ1，ｔ2および周波数ｆ2の信号成分４１４と、時間ｔ1，ｔ2および周波数ｆ2のノイズ４２４と、が含まれる。受信信号ｒ1～ｒ4は、たとえば下記（２）式により表すことができる。 Received signal r 4 is a received component at times t 1 and t 2 and frequency f 2 . The received signal r 4, and the time t 1, t 2 and the signal components 414 of the frequency f 2, and noise 424 of time t 1, t 2 and a frequency f 2, contains. The received signals r 1 to r 4 can be expressed by the following equation (2), for example.
Figure JPOXMLDOC01-appb-M000002
Figure JPOXMLDOC01-appb-M000002
　この場合に、時間ｔkおよび周波数ｆiにおけるノイズ成分ηk,iは、たとえば下記（３）式を満たす。なお、この場合はｋ＝１，２、ｉ＝１，２である。 In this case, noise components eta k, i at time t k and the frequency f i satisfies, for example the following equation (3). In this case, k = 1, 2, i = 1, 2.
Figure JPOXMLDOC01-appb-M000003
Figure JPOXMLDOC01-appb-M000003
　上述したように、受信装置１０は、たとえばＭＬＤを用いて復号を行う。この場合に、ＡＷＧＮチャネルにおける尤度関数は、ユークリッド距離を最小化することにより、たとえば下記（４）式により表すことができる。ＡＷＧＮはＡｄｄｉｔｉｖｅ　Ｗｈｉｔｅ　Ｇａｕｓｓｉａｎ　Ｎｏｉｓｅ（加法性ホワイトガウスノイズ）の略である。 As described above, the receiving device 10 performs decoding using, for example, MLD. In this case, the likelihood function in the AWGN channel can be expressed by, for example, the following equation (4) by minimizing the Euclidean distance. AWGN is an abbreviation for Additive White Gaussian Noise (Additive White Gaussian Noise).
Figure JPOXMLDOC01-appb-M000004
Figure JPOXMLDOC01-appb-M000004
　受信装置１０は、たとえば、ｈ1，ｈ2と、受信信号ｒ1～ｒ4と、に基づくＭＬＤによってデータｄ1,1，ｄ1,2，ｄ2,1，ｄ2,2を復号する。ｈ1，ｈ2は、たとえば受信装置１０が送信装置１００からのパイロット信号に基づいてチャネル推定を行うことにより得ることができる。受信信号ｒ1～ｒ4は、受信装置１０が送信装置１００から受信したデータ信号を時間および周波数でフィルタリングすることにより得ることができる。 The receiving apparatus 10 decodes the data d 1,1 , d 1,2 , d 2,1 , d 2,2 by MLD based on, for example, h 1 and h 2 and the received signals r 1 to r 4. . h 1, h 2 can be for example the reception apparatus 10 obtained by performing channel estimation based on the pilot signal from the transmitter 100. The reception signals r 1 to r 4 can be obtained by filtering the data signal received by the reception device 10 from the transmission device 100 by time and frequency.
（実施の形態にかかる送信装置（Ｍ＝３）によるウェーブレットパケット変調のチャネル）
　図５は、実施の形態にかかる送信装置（Ｍ＝３）によるウェーブレットパケット変調のチャネルの一例を示す図である。図５においては、一例として３×１のＭＩＳＯ通信システム（Ｍ＝３）について説明する。この場合に、送信装置１００は、３本の送信アンテナ１２１～１２３を備え、送信アンテナ１２１～１２３からそれぞれトランスミッションスライス１３１～１３３の信号を無線送信する。したがって、受信装置１０が受信する信号には、トランスミッションスライス１３１～１３３が合成されたトランスミッションブロック３１と、ノイズ３２と、が含まれる。 (Channel for Wavelet Packet Modulation by Transmitter (M = 3) According to Embodiment)
FIG. 5 is a diagram illustrating an example of a wavelet packet modulation channel by the transmission apparatus (M = 3) according to the embodiment. In FIG. 5, a 3 × 1 MISO communication system (M = 3) will be described as an example. In this case, transmission apparatus 100 includes three transmission antennas 121 to 123, and wirelessly transmits signals of transmission slices 131 to 133 from transmission antennas 121 to 123, respectively. Therefore, the signal received by the receiving apparatus 10 includes the transmission block 31 in which the transmission slices 131 to 133 are synthesized and the noise 32.
　この場合に、トランスミッションスライス１３１には、それぞれデータｄ1,1～ｄ1,4がマッピングされた４つのサブキャリアが含まれる。トランスミッションスライス１３２には、それぞれデータｄ2,1～ｄ2,4がマッピングされた４つのサブキャリアが含まれる。トランスミッションスライス１３３には、それぞれデータｄ3,1～ｄ3,4がマッピングされた４つのサブキャリアが含まれる。 In this case, the transmission slice 131 includes four subcarrier data d 1,1 ~ d 1,4 is mapped respectively. Transmission slice 132 includes four subcarriers each mapped with data d 2,1 to d 2,4 . Transmission slice 133 includes four subcarriers each mapped with data d 3,1 to d 3,4 .
　受信装置１０は、たとえば、ｈ1～ｈ3と、各受信信号と、に基づくＭＬＤによってデータｄ1,1～ｄ1,4，ｄ2,1～ｄ2,4，ｄ3,1～ｄ3,4を復号する。ｈ1～ｈ3は、たとえば受信装置１０が送信装置１００からのパイロット信号に基づいてチャネル推定を行うことにより得ることができる。各受信信号は、受信装置１０が送信装置１００から受信したデータ信号を時間および周波数でフィルタリングすることにより得ることができる。 For example, the receiving apparatus 10 uses the data L 1,1 to d 1,4 , d 2,1 to d 2,4 , d 3,1 to d by MLD based on h 1 to h 3 and each received signal. Decrypt 3,4 . h 1 to h 3 can be obtained, for example, when the receiving apparatus 10 performs channel estimation based on a pilot signal from the transmitting apparatus 100. Each received signal can be obtained by filtering the data signal received from the transmitting apparatus 100 by the receiving apparatus 10 by time and frequency.
（実施の形態にかかる送信装置の送信機）
　図６は、実施の形態にかかる送信装置の送信機の一例を示す図である。Ｍ×１のＭＩＳＯ通信システムにおいて、送信機１１０は、たとえば、図６に示すように、変調チャネル符号化部６１１～６１Ｍと、逆ウェーブレットパケット変換部６２１～６２Ｍ（ＩＷＰＴ）と、デジタル／アナログ変換器６３１～６３Ｍ（Ｄ／Ａ）とを備える。ＩＷＰＴはＩｎｖｅｒｓｅ　Ｗａｖｅｌｅｔ　Ｐａｃｋｅｔ　Ｔｒａｎｓｆｏｒｍ（逆ウェーブレットパケット変換）の略である。 (Transmitter of transmitting apparatus according to embodiment)
FIG. 6 is a diagram illustrating an example of the transmitter of the transmission apparatus according to the embodiment. In the M × 1 MISO communication system, for example, as shown in FIG. 6, the transmitter 110 includes modulation channel encoding units 611 to 61M, inverse wavelet packet conversion units 621 to 62M (IWPT), and digital / analog conversion. And 631 to 63M (D / A). IWPT is an abbreviation for inverse wavelet packet transform (inverse wavelet packet transform).
　変調チャネル符号化部６１１～６１Ｍおよび逆ウェーブレットパケット変換部６２１～６２Ｍは、一例としてはＦＰＧＡ、ＤＳＰ、ＣＰＵなどのデジタルプロセッサによって実現することができる。ＦＰＧＡはＦｉｅｌｄ　Ｐｒｏｇｒａｍｍａｂｌｅ　Ｇａｔｅ　Ａｒｒａｙの略である。ＤＳＰはＤｉｇｉｔａｌ　Ｓｉｇｎａｌ　Ｐｒｏｃｅｓｓｏｒの略である。ＣＰＵはＣｅｎｔｒａｌ　Ｐｒｏｃｅｓｓｉｎｇ　Ｕｎｉｔ（中央処理装置）の略である。 The modulation channel encoding units 611 to 61M and the inverse wavelet packet conversion units 621 to 62M can be realized by a digital processor such as an FPGA, DSP, or CPU, for example. FPGA is an abbreviation for Field Programmable Gate Array. DSP is an abbreviation for Digital Signal Processor. CPU is an abbreviation for Central Processing Unit (Central Processing Unit).
　変調チャネル符号化部６１１には第１データ（ＤＡＴＡ－１）が入力される。変調チャネル符号化部６１１は、入力された第１データのチャネル符号化を行い、チャネル符号化により得られた信号を逆ウェーブレットパケット変換部６２１へ出力する。変調チャネル符号化部６１１が逆ウェーブレットパケット変換部６２１へ出力する信号は、たとえば図２に示した２M-1個のサブキャリア２０１に対応する２M-1個の信号である。 The first data (DATA-1) is input to the modulation channel encoding unit 611. Modulation channel coding section 611 performs channel coding of the input first data, and outputs a signal obtained by channel coding to inverse wavelet packet transform section 621. The signal output from the modulation channel encoding unit 611 to the inverse wavelet packet conversion unit 621 is, for example, 2 M−1 signals corresponding to the 2 M−1 subcarriers 201 illustrated in FIG.
　同様に、変調チャネル符号化部６１２～６１Ｍには、それぞれ第２～第Ｍデータ（ＤＡＴＡ－２～ＤＡＴＡ－Ｍ）が入力される。変調チャネル符号化部６１２～６１Ｍは、それぞれ入力された第２～第Ｍデータのチャネル符号化を行い、チャネル符号化により得られた信号をそれぞれ逆ウェーブレットパケット変換部６２２～６２Ｍへ出力する。 Similarly, second to Mth data (DATA-2 to DATA-M) are input to modulation channel encoding sections 612 to 61M, respectively. Modulation channel coding sections 612 to 61M perform channel coding of the input second to Mth data, respectively, and output signals obtained by channel coding to inverse wavelet packet transform sections 622 to 62M, respectively.
　逆ウェーブレットパケット変換部６２１～６２Ｍは、それぞれ変調チャネル符号化部６１１～６１Ｍから出力された各信号に対して、互いに異なるウェーブレットパケット（ＷＰ－１～ＷＰ－Ｍ）に基づく逆ウェーブレットパケット変換を行う。逆ウェーブレットパケット変換部６２１～６２Ｍによる逆ウェーブレットパケット変換により、それぞれトランスミッションスライス１３１～１３Ｍの信号が得られる。 Inverse wavelet packet converters 621 to 62M perform inverse wavelet packet conversion based on different wavelet packets (WP-1 to WP-M) for the signals output from modulation channel encoders 611 to 61M, respectively. . Signals of transmission slices 131 to 13M are obtained by inverse wavelet packet conversion by the inverse wavelet packet converters 621 to 62M, respectively.
　たとえば、逆ウェーブレットパケット変換部６２１～６２Ｍは、互いに異なる回数だけ直交ミラーフィルタの演算を繰り返すことにより逆ウェーブレット変換を行う。一例としては、逆ウェーブレットパケット変換部６２１～６２Ｍは、それぞれ１回～Ｍ回、直交ミラーフィルタの演算を繰り返すことにより逆ウェーブレット変換を行う。これにより、たとえば図２に示したトランスミッションスライス１３１～１３３の信号を得ることができる。逆ウェーブレットパケット変換部６２１～６２Ｍは、それぞれトランスミッションスライス１３１～１３３の信号をそれぞれデジタル／アナログ変換器６３１～６３Ｍへ出力する。 For example, the inverse wavelet packet transform units 621 to 62M perform inverse wavelet transform by repeating the operation of the orthogonal mirror filter a different number of times. As an example, the inverse wavelet packet transform units 621 to 62M perform inverse wavelet transform by repeating the operation of the orthogonal mirror filter once to M times, respectively. Thereby, for example, the signals of transmission slices 131 to 133 shown in FIG. 2 can be obtained. The inverse wavelet packet converters 621 to 62M output the signals of the transmission slices 131 to 133 to the digital / analog converters 631 to 63M, respectively.
　デジタル／アナログ変換器６３１は、逆ウェーブレットパケット変換部６２１から出力された信号をデジタル信号からアナログ信号に変換し、変換した信号を送信アンテナ１２１へ出力する。同様に、デジタル／アナログ変換器６３２～６３Ｍは、それぞれ逆ウェーブレットパケット変換部６２２～６２Ｍから出力された信号をデジタル信号からアナログ信号に変換し、変換した信号をそれぞれ送信アンテナ１２２～１２Ｍへ出力する。デジタル／アナログ変換器６３１～６３Ｍから送信アンテナ１２１～１２Ｍへ出力された各信号は、それぞれ変調されて送信アンテナ１２１～１２Ｍから無線送信される。 The digital / analog converter 631 converts the signal output from the inverse wavelet packet conversion unit 621 from a digital signal to an analog signal, and outputs the converted signal to the transmission antenna 121. Similarly, the digital / analog converters 632 to 63M convert the signals output from the inverse wavelet packet converters 622 to 62M from digital signals to analog signals, respectively, and output the converted signals to the transmission antennas 122 to 12M, respectively. . The signals output from the digital / analog converters 631 to 63M to the transmission antennas 121 to 12M are modulated and wirelessly transmitted from the transmission antennas 121 to 12M.
　図６に示したように、離散領域における送信信号は、チャネル符号化された後、異なるウェーブレットパケットに基づく逆ウェーブレットパケット変換により、２M-1個の波形の和である連続した変調シンボルから構成される。すなわち、第ｋデータ（ＤＡＴＡ－ｋ）は第ｋウェーブレットパケットに基づくＩＷＰＴにより操作される。 As shown in FIG. 6, the transmission signal in the discrete domain is composed of continuous modulation symbols that are the sum of 2 M-1 waveforms after channel coding and by inverse wavelet packet transformation based on different wavelet packets. Is done. That is, the kth data (DATA-k) is manipulated by the IWPT based on the kth wavelet packet.
（実施の形態にかかる受信装置の受信機）
　図７は、実施の形態にかかる受信装置の受信機の一例を示す図である。Ｍ×１のＭＩＳＯシステムにおいて、受信機１２は、たとえば、図７に示すように、アナログ／デジタル変換器７１０（Ａ／Ｄ）と、ウェーブレットパケット変換部７２１～７２Ｍ（ＷＰＴ）と、ＭＬＤ復号部７３０と、を備える。ＷＰＴはＷａｖｅｌｅｔ　Ｐａｃｋｅｔ　Ｔｒａｎｓｆｏｒｍ（ウェーブレットパケット変換）の略である。ウェーブレットパケット変換部７２１～７２ＭおよびＭＬＤ復号部７３０は、一例としてはＦＰＧＡ、ＤＳＰ、ＣＰＵなどのデジタルプロセッサによって実現することができる。 (Receiver of receiving apparatus according to embodiment)
FIG. 7 is a diagram illustrating an example of a receiver of the receiving apparatus according to the embodiment. In the M × 1 MISO system, for example, as shown in FIG. 7, the receiver 12 includes an analog / digital converter 710 (A / D), wavelet packet converters 721 to 72M (WPT), and an MLD decoder. 730. WPT is an abbreviation for Wavelet Packet Transform. For example, the wavelet packet conversion units 721 to 72M and the MLD decoding unit 730 can be realized by a digital processor such as an FPGA, a DSP, or a CPU.
　アナログ／デジタル変換器７１０は、受信アンテナ１１から出力された信号をアナログ信号からデジタル信号に変換し、変換した信号をウェーブレットパケット変換部７２１～７２Ｍへ出力する。アナログ／デジタル変換器７１０からウェーブレットパケット変換部７２１～７２Ｍへ出力される信号には、トランスミッションブロック３１およびノイズ３２（たとえばＡＷＧＮノイズ）が含まれる。 Analog / digital converter 710 converts the signal output from reception antenna 11 from an analog signal to a digital signal, and outputs the converted signal to wavelet packet conversion units 721 to 72M. The signal output from the analog / digital converter 710 to the wavelet packet converters 721 to 72M includes the transmission block 31 and noise 32 (for example, AWGN noise).
　ウェーブレットパケット変換部７２１～７２Ｍは、アナログ／デジタル変換器７１０から出力された信号に対して、互いに異なるウェーブレットパケット（ＷＰ－１～ＷＰ－Ｍ）に基づくウェーブレットパケット変換（ＷＰＴ）を行う。ウェーブレットパケット変換部７２１～７２Ｍが用いるウェーブレットパケット（ＷＰ－１～ＷＰ－Ｍ）は、たとえばそれぞれ逆ウェーブレットパケット変換部６２１～６２Ｍ（図６参照）が用いるウェーブレットパケットに対応するウェーブレットパケットである。ウェーブレットパケット変換部７２１～７２Ｍのそれぞれは、ウェーブレットパケット変換により得られた信号（サブキャリア波形）をＭＬＤ復号部７３０へ出力する。 The wavelet packet conversion units 721 to 72M perform wavelet packet conversion (WPT) based on different wavelet packets (WP-1 to WP-M) on the signal output from the analog / digital converter 710. The wavelet packets (WP-1 to WP-M) used by the wavelet packet conversion units 721 to 72M are wavelet packets corresponding to the wavelet packets used by the inverse wavelet packet conversion units 621 to 62M (see FIG. 6), respectively. Each of the wavelet packet conversion units 721 to 72M outputs a signal (subcarrier waveform) obtained by the wavelet packet conversion to the MLD decoding unit 730.
　ＭＬＤ復号部７３０は、ウェーブレットパケット変換部７２１～７２Ｍから出力された各信号に基づくＭＬＤにより、第１～第Ｍデータの復号結果ＤＡＴＡ－１’～ＤＡＴＡ－Ｍ’を得る。また、ＭＬＤ復号部７３０は、得られた復号結果ＤＡＴＡ－１’～ＤＡＴＡ－Ｍ’を出力する。 The MLD decoding unit 730 obtains the decoding results DATA-1 ′ to DATA-M ′ of the first to Mth data by MLD based on the signals output from the wavelet packet conversion units 721 to 72M. Further, the MLD decoding unit 730 outputs the obtained decoding results DATA-1 ′ to DATA-M ′.
（ウェーブレットパケット）
　ウェーブレットパケットについて説明する。上述した逆ウェーブレットパケット変換部６２１～６２Ｍやウェーブレットパケット変換部７２１～７２Ｍにおけるウェーブレット変換には、たとえば離散ウェーブレットパケット変換を用いることができる。一対のウェーブレットフィルタであるｈ［ｎ］およびｇ［ｎ］は、それぞれ直交ミラーフィルタ（Ｑｕａｄｒａｔｕｒｅ　Ｍｉｒｒｏｒ　Ｆｉｌｔｅｒ）特性を有するハイパスフィルタおよびローパスフィルタに属する。ｈ［ｎ］およびｇ［ｎ］の間の関係は、たとえば下記（５）式により表される。 (Wavelet packet)
The wavelet packet will be described. For example, discrete wavelet packet conversion can be used for wavelet conversion in the above-described inverse wavelet packet conversion units 621 to 62M and wavelet packet conversion units 721 to 72M. A pair of wavelet filters h [n] and g [n] belong to a high-pass filter and a low-pass filter each having a quadrature mirror filter characteristic. The relationship between h [n] and g [n] is expressed by the following equation (5), for example.
Figure JPOXMLDOC01-appb-M000005
Figure JPOXMLDOC01-appb-M000005
　離散ウェーブレットパケット変換（ＤＷＰＴ）においては２j波形の和として信号が構成される。これらの波形は、それぞれフィルタリングとアップサンプリングからなるｊ回の連続反復によって構築することができる。したがって、離散ウェーブレットパケット変換は、たとえば下記（６）式のように再帰的な関数の集合として定義することができる。 In discrete wavelet packet transform (DWPT), a signal is constructed as the sum of 2 j waveforms. These waveforms can be constructed by j successive iterations, each consisting of filtering and upsampling. Accordingly, the discrete wavelet packet transform can be defined as a set of recursive functions, for example, as shown in the following equation (6).
Figure JPOXMLDOC01-appb-M000006
Figure JPOXMLDOC01-appb-M000006
（実施の形態にかかるＳＮＲとシンボルエラーレートとの間の関係）
　図８は、実施の形態にかかるＳＮＲとシンボルエラーレートとの間の関係の一例を示す図である。図８において、横軸はＳＮＲを示し、縦軸はシンボルエラーレートを示している。ＳＮＲはＳｉｇｎａｌ　ｔｏ　Ｎｏｉｓｅ　Ｒａｔｉｏ（信号対雑音比）の略である。図８は、変調方式としてＱＰＳＫ変調を用いた場合の例を示している。ＱＰＳＫはＱｕａｄｒａｔｕｒｅ　Ｐｈａｓｅ　Ｓｈｉｆｔ　Ｋｅｙｉｎｇの略である。 (Relationship between SNR and symbol error rate according to the embodiment)
FIG. 8 is a diagram illustrating an example of a relationship between the SNR and the symbol error rate according to the embodiment. In FIG. 8, the horizontal axis indicates the SNR, and the vertical axis indicates the symbol error rate. SNR is an abbreviation for Signal to Noise Ratio (signal to noise ratio). FIG. 8 shows an example in which QPSK modulation is used as the modulation method. QPSK is an abbreviation for Quadrature Phase Shift Keying.
　ＳＮＲシンボルエラーレート特性８０１は、実施の形態にかかる２×１のＭＩＳＯ通信システム（たとえば図４参照）における、ＳＮＲに対するシンボルエラーレートの特性を示している。ＳＮＲシンボルエラーレート特性８０２は、ＣＳＩをフィードバックしてプリコーディングを行う２×１のＭＩＳＯ通信システムにおける、ＳＮＲに対するシンボルエラーレートの特性を参考として示している。ＳＮＲシンボルエラーレート特性８０３は、ＣＳＩをフィードバックしてプリコーディングを行う１×１のＳＩＳＯ通信システムにおける、ＳＮＲに対するシンボルエラーレートの特性を参考として示している。ＳＩＳＯはＳｉｎｇｌｅ　Ｉｎｐｕｔ　ａｎｄ　Ｓｉｎｇｌｅ　Ｏｕｔｐｕｔ（単一入力単一出力）の略である。 The SNR symbol error rate characteristic 801 indicates the characteristic of the symbol error rate with respect to the SNR in the 2 × 1 MISO communication system (for example, see FIG. 4) according to the embodiment. The SNR symbol error rate characteristic 802 shows the symbol error rate characteristic with respect to the SNR in a 2 × 1 MISO communication system that performs precoding by feeding back CSI. An SNR symbol error rate characteristic 803 indicates a symbol error rate characteristic with respect to an SNR in a 1 × 1 SISO communication system that performs precoding by feeding back CSI. SISO is an abbreviation for Single Input and Single Output (single input single output).
　図９は、実施の形態にかかるＳＮＲとシンボルエラーレートとの間の関係の他の一例を示す図である。図９において、横軸はＳＮＲを示し、縦軸はシンボルエラーレートを示している。図９は、変調方式として１６ＱＡＭ変調を用いた場合の例を示している。ＱＡＭはＱｕａｄｒａｔｕｒｅ　Ａｍｐｌｉｔｕｄｅ　Ｍｏｄｕｌａｔｉｏｎ（直角位相振幅変調）の略である。 FIG. 9 is a diagram illustrating another example of the relationship between the SNR and the symbol error rate according to the embodiment. In FIG. 9, the horizontal axis indicates the SNR, and the vertical axis indicates the symbol error rate. FIG. 9 shows an example in which 16QAM modulation is used as the modulation method. QAM is an abbreviation for Quadrature Amplitude Modulation.
　ＳＮＲシンボルエラーレート特性９０１は、実施の形態にかかる２×１のＭＩＳＯ通信システム（たとえば図４参照）における、ＳＮＲに対するシンボルエラーレートの特性を示している。ＳＮＲシンボルエラーレート特性９０２は、ＣＳＩをフィードバックしてプリコーディングを行う２×１のＭＩＳＯ通信システムにおける、ＳＮＲに対するシンボルエラーレートの特性を参考として示している。ＳＮＲシンボルエラーレート特性９０３は、ＣＳＩをフィードバックしてプリコーディングを行う１×１のＳＩＳＯ通信システムにおける、ＳＮＲに対するシンボルエラーレートの特性を参考として示している。 The SNR symbol error rate characteristic 901 indicates the symbol error rate characteristic with respect to the SNR in the 2 × 1 MISO communication system (see FIG. 4 for example) according to the embodiment. An SNR symbol error rate characteristic 902 shows a symbol error rate characteristic with respect to SNR in a 2 × 1 MISO communication system that performs precoding by feeding back CSI. An SNR symbol error rate characteristic 903 indicates a symbol error rate characteristic with respect to an SNR in a 1 × 1 SISO communication system that performs precoding by feeding back CSI.
　図１０は、実施の形態にかかるＳＮＲとシンボルエラーレートとの間の関係のさらに他の一例を示す図である。図１０において、横軸はＳＮＲを示し、縦軸はシンボルエラーレートを示している。図１０は、変調方式としてＱＰＳＫ変調を用いた場合の例を示している。 FIG. 10 is a diagram illustrating still another example of the relationship between the SNR and the symbol error rate according to the embodiment. In FIG. 10, the horizontal axis indicates the SNR, and the vertical axis indicates the symbol error rate. FIG. 10 shows an example in which QPSK modulation is used as the modulation method.
　ＳＮＲシンボルエラーレート特性１００１は、実施の形態にかかる３×１のＭＩＳＯ通信システム（たとえば図５参照）における、ＳＮＲに対するシンボルエラーレートの特性を示している。ＳＮＲシンボルエラーレート特性１００２は、ＣＳＩをフィードバックしてプリコーディングを行う３×１のＭＩＳＯ通信システムにおける、ＳＮＲに対するシンボルエラーレートの特性を参考として示している。ＳＮＲシンボルエラーレート特性１００３は、ＣＳＩをフィードバックしてプリコーディングを行う１×１のＳＩＳＯ通信システムにおける、ＳＮＲに対するシンボルエラーレートの特性を参考として示している。 The SNR symbol error rate characteristic 1001 indicates the characteristic of the symbol error rate with respect to the SNR in the 3 × 1 MISO communication system (see, for example, FIG. 5) according to the embodiment. An SNR symbol error rate characteristic 1002 shows a symbol error rate characteristic with respect to an SNR in a 3 × 1 MISO communication system that performs precoding by feeding back CSI. An SNR symbol error rate characteristic 1003 shows a symbol error rate characteristic with respect to an SNR in a 1 × 1 SISO communication system that performs precoding by feeding back CSI.
　図８～図１０に示すように、実施の形態にかかるＭＩＳＯ通信システムは、たとえば各送信アンテナからの送信電力を同じとすると、１×１のＳＩＳＯ通信システムの最良のケースに近い性能が得られる。したがって、実施の形態にかかるＭＩＳＯ通信システムは、ＣＳＩ等のフィードバックを行わなくても、ＣＳＩ等のフィードバックを行うＭＩＳＯ等と同様の容量を達成することができる。 As shown in FIGS. 8 to 10, the MISO communication system according to the embodiment can achieve performance close to the best case of the 1 × 1 SISO communication system, for example, when the transmission power from each transmission antenna is the same. . Therefore, the MISO communication system according to the embodiment can achieve the same capacity as MISO that performs feedback such as CSI without performing feedback such as CSI.
　また、実施の形態にかかるＭＩＳＯ通信システムは、変調方式としてＱＰＳＫ変調を用いる場合に特に高い性能が得られる。また、実施の形態にかかるＭＩＳＯ通信システムは、送信アンテナの数が多くなるほど、変調に伴う時間と周波数のサイズが大きくなるため利得が高くなる。 Also, the MISO communication system according to the embodiment can obtain particularly high performance when QPSK modulation is used as a modulation method. In the MISO communication system according to the embodiment, as the number of transmission antennas increases, the time and frequency size associated with modulation increase, and thus the gain increases.
　このように、実施の形態によれば、データを割り当てる無線リソース単位（サブキャリア）における時間長と帯域幅との積が互いに同じで時間長と帯域幅との組み合わせが互いに異なる複数の信号を逆ウェーブレット変換により生成することができる。そして、生成した複数の信号をそれぞれ複数のアンテナから送信することができる。これにより、たとえば受信装置１０から送信装置１００へＣＳＩなどのフィードバック信号を送信しなくても、伝送品質（たとえば誤り率）の向上を図ることができる。 Thus, according to the embodiment, a plurality of signals having the same product of time length and bandwidth and different combinations of time length and bandwidth in the radio resource unit (subcarrier) to which data is allocated are reversed. It can be generated by wavelet transform. A plurality of generated signals can be transmitted from a plurality of antennas. Thereby, transmission quality (for example, error rate) can be improved without transmitting a feedback signal such as CSI from the receiving apparatus 10 to the transmitting apparatus 100, for example.
　以上説明したように、基地局、端末、送信プログラム、受信プログラム、送信方法および受信方法によれば、チャネル状態情報のフィードバックがなくても伝送品質の向上を図ることができる。 As described above, according to the base station, terminal, transmission program, reception program, transmission method, and reception method, transmission quality can be improved without feedback of channel state information.
　たとえば、ＭＩＭＯの技術は既にＩＥＥＥ　８０２．１６ｍなどの多くの規格で採用されている。ＭＩＭＯはＭｕｌｔｉｐｌｅ　Ｉｎｐｕｔ　Ｍｕｌｔｉｐｌｅ　Ｏｕｔｐｕｔ（複数入力複数出力）の略である。ＩＥＥＥはｔｈｅ　Ｉｎｓｔｉｔｕｔｅ　ｏｆ　Ｅｌｅｃｔｒｉｃａｌ　ａｎｄ　Ｅｌｅｃｔｒｏｎｉｃｓ　Ｅｎｇｉｎｅｅｒｓの略である。実際のシステムにおいては、ＭＩＭＯの実装および性能は、ＣＳＩがどの程度フィードバックされ得るかに依存する。ＣＳＩによる十分なフィールドバックがある場合に、線形プリコーディングＭＩＭＯ方式は、たとえばＺＦ、ＭＭＳＥまたはＳＶＤにより実施される。しかし、ＣＳＩのフィードバックには多くのオーバーヘッドを要する。ＺＦはＺｅｒｏ　Ｆｏｒｃｉｎｇ（ゼロフォーシング）の略である。ＭＭＳＥはＭｉｎｉｍｕｍ　Ｍｅａｎ　Ｓｑｕａｒｅ　Ｅｒｒｏｒ（最小二乗誤差法）の略である。ＳＶＤはＳｉｎｇｕｌａｒ　Ｖａｌｕｅ　Ｄｅｃｏｍｐｏｓｉｔｉｏｎ（特異値分解）の略である。 For example, MIMO technology has already been adopted in many standards such as IEEE 802.16m. MIMO stands for Multiple Input Multiple Output (multiple input multiple output). IEEE is an abbreviation for the Institute of Electrical and Electronics Engineers. In an actual system, the implementation and performance of MIMO depends on how much CSI can be fed back. The linear precoding MIMO scheme is implemented by, for example, ZF, MMSE or SVD when there is sufficient fieldback due to CSI. However, CSI feedback requires a lot of overhead. ZF is an abbreviation for Zero Forcing. MMSE is an abbreviation for Minimum Mean Square Error (least square error method). SVD is an abbreviation for Single Value Decomposition.
　これに対して、実施の形態によれば、ウェーブレット空間に基づく周波数と時間変調伝送を考慮した効率的な伝送により、ＣＳＩのフィードバックを行わなくても高い容量利得を実現することができる。 On the other hand, according to the embodiment, high capacity gain can be realized without performing CSI feedback by efficient transmission considering frequency and time modulation transmission based on wavelet space.
　なお、本実施の形態で説明した送信方法や受信方法は、予め用意されたプログラムを通信装置のコンピュータで実行することにより実現することができる。このプログラムは、ハードディスク、フレキシブルディスク、ＣＤ－ＲＯＭ、ＤＶＤ等のコンピュータで読み取り可能な記録媒体に記録され、コンピュータによって記録媒体から読み出されることによって実行される。ＣＤ－ＲＯＭはＣｏｍｐａｃｔ　Ｄｉｓｃ－Ｒｅａｄ　Ｏｎｌｙ　Ｍｅｍｏｒｙの略である。ＤＶＤはＤｉｇｉｔａｌ　Ｖｅｒｓａｔｉｌｅ　Ｄｉｓｃの略である。またこのプログラムは、インターネット等のネットワークを介して配布することが可能な伝送媒体であってもよい。 Note that the transmission method and the reception method described in this embodiment can be realized by executing a program prepared in advance on a computer of a communication apparatus. This program is recorded on a computer-readable recording medium such as a hard disk, a flexible disk, a CD-ROM, and a DVD, and is executed by being read from the recording medium by the computer. CD-ROM is an abbreviation for Compact Disc-Read Only Memory. DVD is an abbreviation for Digital Versatile Disc. The program may be a transmission medium that can be distributed via a network such as the Internet.
　１０　受信装置
　１１　受信アンテナ
　１２　受信機
　３１　トランスミッションブロック
　３２，４２１～４２４　ノイズ
　１００　送信装置
　１１０　送信機
　１２１～１２Ｍ　送信アンテナ
　１３１～１３Ｍ　トランスミッションスライス
　２０１～２０Ｍ　サブキャリア
　４１１～４１４　信号成分
　６１１～６１Ｍ　変調チャネル符号化部
　６２１～６２Ｍ　逆ウェーブレットパケット変換部
　６３１～６３Ｍ　デジタル／アナログ変換器
　７１０　アナログ／デジタル変換器
　７２１～７２Ｍ　ウェーブレットパケット変換部
　７３０　ＭＬＤ復号部
　８０１～８０３，９０１～９０３，１００１～１００３　ＳＮＲシンボルエラーレート特性 DESCRIPTION OF SYMBOLS 10 Receiver 11 Receiver antenna 12 Receiver 31 Transmission block 32,421-424 Noise 100 Transmitter 110 Transmitter 121-12M Transmit antenna 131-13M Transmission slice 201-20M Subcarrier 411-414 Signal component 611-61M Modulation channel code Conversion unit 621 to 62M Inverse wavelet packet conversion unit 631 to 63M Digital / analog converter 710 Analog / digital converter 721 to 72M Wavelet packet conversion unit 730 MLD decoding unit 801 to 803, 901 to 903, 1001 to 1003 SNR symbol error rate Characteristic

Claims (10)

  1. 　データを割り当てる無線リソース単位における時間長と帯域幅との積が互いに同じであり、かつ前記無線リソース単位における時間長と帯域幅との組み合わせが互いに異なる複数の信号を逆ウェーブレット変換により生成する生成部と、
    　前記生成部によって生成された前記複数の信号をそれぞれ送信する複数のアンテナと、
    　を備えることを特徴とする基地局。     Generating unit for generating a plurality of signals by inverse wavelet transform in which a product of time length and bandwidth in a radio resource unit to which data is allocated is the same, and a combination of time length and bandwidth in the radio resource unit is different from each other When,
    A plurality of antennas respectively transmitting the plurality of signals generated by the generation unit;
    A base station comprising:
  2. 　前記複数の信号は、第１信号と、前記無線リソース単位における時間長が前記第１信号の２倍であり前記無線リソース単位における帯域幅が前記第１信号の半分である第２信号と、を含み、
    　前記複数のアンテナは、前記第１信号を送信する第１アンテナと、前記第１アンテナと隣接し前記第２信号を送信する第２アンテナと、を含む、
    　ことを特徴とする請求項１に記載の基地局。     The plurality of signals include a first signal and a second signal having a time length in the radio resource unit that is twice that of the first signal and a bandwidth in the radio resource unit that is half that of the first signal. Including
    The plurality of antennas includes a first antenna that transmits the first signal, and a second antenna that is adjacent to the first antenna and transmits the second signal.
    The base station according to claim 1.
  3. 　前記複数の信号は、前記逆ウェーブレット変換における直交ミラーフィルタの演算の繰り返し回数が互いに異なる各信号であることを特徴とする請求項１または２に記載の基地局。 The base station according to claim 1 or 2, wherein the plurality of signals are signals having different numbers of repetitions of the operation of the orthogonal mirror filter in the inverse wavelet transform.
  4. 　前記複数のアンテナは等間隔で配置された第１～第Ｍアンテナを含み、
    　前記複数の信号は、それぞれ前記第１～第Ｍアンテナにより送信される第１～第Ｍ信号を含み、
    　前記第１～第Ｍ信号のうちの第ｍ信号は、前記無線リソース単位における時間長が前記第１信号の２m-1倍であり前記無線リソース単位における帯域幅が前記第１信号の２m-1分の１である、
    　ことを特徴とする請求項１～３のいずれか一つに記載の基地局。     The plurality of antennas include first to Mth antennas arranged at equal intervals,
    The plurality of signals include first to Mth signals transmitted by the first to Mth antennas, respectively.
    The m-th signal among the first to M-th signals has a time length in the radio resource unit of 2 m-1 times that of the first signal, and a bandwidth in the radio resource unit is 2 m of the first signal. Is -1
    The base station according to any one of claims 1 to 3, wherein:
  5. 　データを割り当てる無線リソース単位における時間長と帯域幅との積が互いに同じであり、かつ前記無線リソース単位における時間長と帯域幅との組み合わせが互いに異なる複数の信号を逆ウェーブレット変換により生成し、生成した前記複数の信号をそれぞれ複数のアンテナにより送信する基地局から前記複数の信号を受信する受信部と、
    　前記受信部によって受信された信号を復号する復号部と、
    　を備えることを特徴とする端末。     Generate and generate multiple signals by inverse wavelet transform with the same product of time length and bandwidth in the radio resource unit to which data is allocated, and different combinations of time length and bandwidth in the radio resource unit A receiver that receives the plurality of signals from a base station that transmits the plurality of signals through a plurality of antennas, respectively;
    A decoding unit for decoding the signal received by the receiving unit;
    A terminal comprising:
  6. 　前記復号部はＭＬＤ（Ｍａｘｉｍｕｍ　Ｌｉｋｅｌｉｈｏｏｄ　Ｄｅｔｅｃｔｉｏｎ）により前記信号を復号することを特徴とする請求項５に記載の端末。 The terminal according to claim 5, wherein the decoding unit decodes the signal by MLD (Maximum Likelihood Detection).
  7. 　データを割り当てる無線リソース単位における時間長と帯域幅との積が互いに同じであり、かつ前記無線リソース単位における時間長と帯域幅との組み合わせが互いに異なる複数の信号を逆ウェーブレット変換により生成し、
    　生成した前記複数の信号をそれぞれ複数のアンテナにより送信する、
    　処理をコンピュータに実行させることを特徴とする送信プログラム。     A product of time length and bandwidth in a radio resource unit to which data is allocated is the same as each other, and a plurality of signals having different combinations of time length and bandwidth in the radio resource unit are generated by inverse wavelet transform,
    Transmitting the plurality of generated signals through a plurality of antennas, respectively;
    A transmission program that causes a computer to execute processing.
  8. 　データを割り当てる無線リソース単位における時間長と帯域幅との積が互いに同じであり、かつ前記無線リソース単位における時間長と帯域幅との組み合わせが互いに異なる複数の信号を逆ウェーブレット変換により生成し、生成した前記複数の信号をそれぞれ複数のアンテナにより送信する送信装置から前記複数の信号を受信し、
    　受信した信号を復号する、
    　処理をコンピュータに実行させることを特徴とする受信プログラム。     Generate and generate multiple signals by inverse wavelet transform with the same product of time length and bandwidth in the radio resource unit to which data is allocated, and different combinations of time length and bandwidth in the radio resource unit Receiving the plurality of signals from a transmitting device that transmits the plurality of signals through a plurality of antennas, respectively.
    Decode the received signal,
    A receiving program for causing a computer to execute processing.
  9. 　送信装置が、
    　データを割り当てる無線リソース単位における時間長と帯域幅との積が互いに同じであり、かつ前記無線リソース単位における時間長と帯域幅との組み合わせが互いに異なる複数の信号を逆ウェーブレット変換により生成し、
    　生成した前記複数の信号をそれぞれ複数のアンテナにより送信する、
    　ことを特徴とする送信方法。     The transmitting device is
    A product of time length and bandwidth in a radio resource unit to which data is allocated is the same as each other, and a plurality of signals having different combinations of time length and bandwidth in the radio resource unit are generated by inverse wavelet transform,
    Transmitting the plurality of generated signals through a plurality of antennas, respectively;
    A transmission method characterized by the above.
  10. 　受信装置が、
    　データを割り当てる無線リソース単位における時間長と帯域幅との積が互いに同じであり、かつ前記無線リソース単位における時間長と帯域幅との組み合わせが互いに異なる複数の信号を逆ウェーブレット変換により生成し、生成した前記複数の信号をそれぞれ複数のアンテナにより送信する送信装置から前記複数の信号を受信し、
    　受信した信号を復号する、
    　ことを特徴とする受信方法。     The receiving device
    Generate and generate multiple signals by inverse wavelet transform with the same product of time length and bandwidth in the radio resource unit to which data is allocated, and different combinations of time length and bandwidth in the radio resource unit Receiving the plurality of signals from a transmitting device that transmits the plurality of signals through a plurality of antennas, respectively.
    Decode the received signal,
    And a receiving method.
PCT/JP2017/015374 2017-04-14 2017-04-14 Base station, terminal, transmission program, reception program, transmission method, and reception method WO2018189905A1 (en)

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Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH08214308A (en) * 1995-02-06 1996-08-20 Matsushita Graphic Commun Syst Inc Image compression encoder and image expansion decoder
JPH11252031A (en) * 1998-03-05 1999-09-17 Toyota Central Res & Dev Lab Inc Receiving machine
JP2013232915A (en) * 2010-01-08 2013-11-14 Panasonic Corp Ofdm transmitter, ofdm transmission method, ofdm receiver and ofdm reception method
WO2017056796A1 (en) * 2015-10-01 2017-04-06 ソニー株式会社 Device, method and program

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH08214308A (en) * 1995-02-06 1996-08-20 Matsushita Graphic Commun Syst Inc Image compression encoder and image expansion decoder
JPH11252031A (en) * 1998-03-05 1999-09-17 Toyota Central Res & Dev Lab Inc Receiving machine
JP2013232915A (en) * 2010-01-08 2013-11-14 Panasonic Corp Ofdm transmitter, ofdm transmission method, ofdm receiver and ofdm reception method
WO2017056796A1 (en) * 2015-10-01 2017-04-06 ソニー株式会社 Device, method and program

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