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WO2018109864A1 - Dispositif de conversion de puissance - Google Patents

Dispositif de conversion de puissance Download PDF

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Publication number
WO2018109864A1
WO2018109864A1 PCT/JP2016/087215 JP2016087215W WO2018109864A1 WO 2018109864 A1 WO2018109864 A1 WO 2018109864A1 JP 2016087215 W JP2016087215 W JP 2016087215W WO 2018109864 A1 WO2018109864 A1 WO 2018109864A1
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WO
WIPO (PCT)
Prior art keywords
switching element
control
reactor
reactor current
current
Prior art date
Application number
PCT/JP2016/087215
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English (en)
Japanese (ja)
Inventor
章太 渡辺
義章 石黒
友一 坂下
前田　貴史
陽 山上
達也 平山
Original Assignee
三菱電機株式会社
三菱電機照明株式会社
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
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Publication date
Application filed by 三菱電機株式会社, 三菱電機照明株式会社 filed Critical 三菱電機株式会社
Priority to PCT/JP2016/087215 priority Critical patent/WO2018109864A1/fr
Priority to JP2017517807A priority patent/JP6186100B1/ja
Publication of WO2018109864A1 publication Critical patent/WO2018109864A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only

Definitions

  • the present invention relates to a power conversion device that has a power factor correction (PFC) function and converts AC power into DC power.
  • PFC power factor correction
  • a full-wave rectifier circuit that full-wave rectifies an AC voltage of an AC power source, a first and a second switching element, and a reactor, and converts an input voltage obtained by the full-wave rectifier circuit into a target output voltage.
  • H-bridge buck-boost converter input voltage after full-wave rectification by the full-wave rectifier circuit, output voltage after voltage conversion by the H-bridge buck-boost converter, and the H-bridge buck-boost converter
  • a detection circuit for detecting each of the reactor currents flowing through the reactor The output voltage is controlled by controlling the first and second switching elements of the H-bridge type buck-boost converter based on the detection signal detected by the detection circuit, and the reactor current is controlled and input.
  • a power conversion device that performs power factor correction control that brings a current waveform close to an input voltage waveform, Based on the comparison between the input voltage and the output voltage, the operation of the step-up control, step-down control, or step-up / step-down control of the H-bridge type step-up / down converter is determined, and the step-up control, step-down control, step-up / step-down control is performed.
  • a method is disclosed in which a target reactor current for individually performing the power factor improvement control corresponding to the time of pressure control is calculated and current control is performed so that the reactor current matches the target reactor current ( For example, see Patent Document 1 below).
  • the first and second switching elements are simultaneously controlled to be turned on / off simultaneously during the step-up / step-down control. Then, assuming that the input / output voltage difference is small during the step-up / down control, the switching duty ratio of the first and second switching elements is about 50%. Therefore, the target reactor current at the time of step-up / step-down control is twice the value corresponding to the input current at the time of step-up control by the first and second switching elements, and twice the value corresponding to the output current at the time of step-down control. It is calculated with. As described above, in the step-up / step-down control, the reactor current flowing through the reactor is doubled in principle as compared with the step-up control and the step-down control, and there is a problem that the loss generated in the reactor increases.
  • the present invention has been made to solve the above-described problems, and provides a power conversion device that can reduce the maximum value of the reactor current flowing through the reactor and reduce the loss generated in the reactor. be able to.
  • the power conversion device comprises a power supply main circuit unit and a power supply control unit,
  • the power supply main circuit unit has a full-wave rectification circuit that full-wave rectifies the AC voltage of the AC power supply, a first switching element and a reactor, and an input voltage obtained by the full-wave rectification circuit.
  • An H-bridge type buck-boost converter that converts the output voltage to an input voltage, an input voltage that has been full-wave rectified by the full-wave rectifier circuit, an output voltage that has been voltage-converted by the H-bridge type buck-boost converter, and the reactor And a detection circuit for detecting a reactor current flowing through
  • the power supply controller controls the output voltage by on / off controlling the first and second switching elements of the H-bridge buck-boost converter based on a detection signal detected by the detection circuit, and controls the output voltage.
  • a power conversion device that performs power factor correction control that controls current to bring an input current waveform closer to an input voltage waveform
  • the power control unit includes a first mode in which both the first and second switching elements are in an on state, a second mode in which the first switching element is in an on state and the second switching element is in an off state,
  • the multi-mode switching control is performed to turn on and off the first and second switching elements so that the second switching elements sequentially have the third mode in the off state.
  • the reactor current is controlled to a square waveform, and the input current waveform is in phase with the input voltage waveform.
  • the power factor can be improved so as to approximate the same waveform.
  • the maximum value of a reactor current can be reduced and the loss which generate
  • FIG. 1 and 2 are circuit block diagrams showing a power supply main circuit section and a power supply control section of the power conversion apparatus according to Embodiment 1 of the present invention.
  • the power conversion device includes a power supply main circuit unit 1 shown in FIG. 1 and a power supply control unit 2 shown in FIG.
  • the power supply main circuit unit 1 has an AC power supply 3 connected to the input side and a load 10 connected to the output side.
  • the power supply main circuit unit 1 includes an input filter 4, a full-wave rectifier circuit 5, an H-bridge type buck-boost converter 6 (hereinafter simply referred to as a converter 6), an input capacitor C1, and an output capacitor C2.
  • the input filter 4 is connected between the AC power supply 3 and the full-wave rectifier circuit 5 to prevent outflow of harmonic currents to the system power supply.
  • the LC is composed of a reactor and a capacitor as shown in FIG. It consists of a filter and the like.
  • the full-wave rectifier circuit 5 is composed of a diode bridge that full-wave rectifies the AC input voltage vac of the AC power supply 3.
  • the input capacitor C1 is connected to the full-wave rectifier circuit 5 and smoothes the switching noise contained in the input voltage
  • the converter 6 is connected to the input capacitor C1.
  • the output capacitor C ⁇ b> 2 is for smoothing the pulsation of the output voltage of the converter 6 to obtain a DC output voltage vdc, and is connected to the converter 6.
  • the load 10 is connected to the output capacitor C2.
  • the full-wave rectifier circuit 5 shows a case where a rectifier circuit in which four diode elements are configured in a full bridge shape is used.
  • the present invention is not limited to this. Any circuit may be used as long as it can perform full-wave rectification.
  • a circuit in which switching elements such as thyristors are combined instead of diodes may be used.
  • the converter 6 has a first arm in which a first switching element Q1 and a first diode D1 are connected in series on the AC power supply side, and a second diode D2 and a second switching element Q2 are connected in series on the load side. A second arm is included.
  • the reactor L is provided between the connection point of the 1st switching element Q1 and the 1st diode D1, and the connection point of the 2nd diode D2 and the 2nd switching element Q2.
  • the first and second switching elements Q1 and Q2 are an FET (Field Effect Transistor) element or an IGBT (Insulated Gate Bipolar Transistor) element driven by a switch signal for on / off control generated by the power supply control unit 2.
  • the converter 6 has a function as a step-up converter and a function as a step-down converter with the above circuit configuration, and adjusts the pulsating voltage
  • FIG. 3 is a graph showing the relationship between the AC input voltage vac and the pulsating voltage
  • the first and second diodes D1 and D2 may be changed to third and fourth switching elements Q3 and Q4 such as FET elements and IGBT elements. That is, converter 6 has a first arm in which first switching element Q1 and third switching element Q3 are connected in series on the AC power supply side, and fourth switching element Q4 and second switching element Q2 are in series on the load side.
  • the reactor L is connected between the connection point of the first switching element Q1 and the third switching element Q3 and the connection point of the fourth switching element Q4 and the second switching element Q2. It becomes the composition which becomes.
  • a synchronous rectification method is employed in which the on / off of the second switching element Q2 and the fourth switching element Q4 is operated with inverse logic and the on / off of the first switching element Q1 and the third switching element Q3 is operated with inverse logic.
  • the power main circuit unit 1 includes a current detection unit 7, an input voltage detection unit 8, and an output voltage detection unit 9, and these detection units correspond to the detection circuit in the claims.
  • the current detector 7 detects a reactor current iL flowing through the reactor L.
  • the input voltage detector 8 detects the magnitude of the pulsating voltage
  • the output voltage detector 9 detects the magnitude of the DC output voltage vdc as an output voltage detection value vo, and includes voltage dividing resistors R3 and R4 connected in series, for example.
  • the power supply control unit 2 compares the output control unit 21 that calculates the output control amount i ** based on the output voltage detection value vo and the target output voltage vo *, and compares the input voltage detection value vin and the output voltage detection value vo. And a first selector 23 and a second selector 26d that switch between step-up control, step-down control, or multi-mode switching control, which is a feature of the present embodiment, based on the result of the comparison unit 22.
  • the power supply control unit 2 also includes a target value calculation unit 24a for calculating the upper limit target value iref *, a reactor current comparison unit 25a for comparing the reactor current iL with the upper limit target value iref * and the lower limit target value, and a reactor during boost control.
  • a switch control unit 26a that generates a signal for controlling the first and second switching elements Q1 and Q2 based on the comparison result of the current comparison unit 25a is provided.
  • the power supply control unit 2 includes a target value calculation unit 24b that calculates the upper limit target value iref *, a reactor current comparison unit 25b that compares the reactor current iL with the upper limit target value iref * and the lower limit target value, and a reactor during step-down control.
  • a switch control unit 26b that generates a signal for controlling the first and second switching elements Q1 and Q2 based on the comparison result of the current comparison unit 25b is provided.
  • the power supply control unit 2 also includes a target value calculation unit 24b that calculates the upper limit target value iref * and a reactor current comparison unit 25b that compares the reactor current iL with the upper limit target value iref * and the lower limit target value during multi-mode switching control.
  • the switch controller 26b generates a signal for controlling the first and second switching elements Q1 and Q2 based on the comparison result of the reactor current comparator 25b.
  • the power supply control unit 2 compares the input voltage detection value vin and the output voltage detection value vo by the comparison unit 22, and switches the contact points of the first selector 23 and the second selector 26d based on the comparison result. Switching between step-up control, step-down control, and multi-mode switching control, which is a feature of the present embodiment. The contents of the multiple mode switching control will be described in detail later.
  • the power supply control unit 2 sets the target value calculation unit 24a during the boost control. Then, the control is switched to the reactor current comparison unit 25a and the switch control unit 26a, and the boost control is performed so that the first switching element Q1 is always turned on and the second switching element Q2 is switched. Further, when the input voltage detection value vin is higher than the output voltage detection value vo by a predetermined value or more (for example, when vin> 1.1 ⁇ vo), the power supply control unit 2 sets the target value calculation unit 24b at the time of step-down control.
  • the power supply control unit 2 performs on / off control of the first and second switching elements Q1 and Q2 of the converter 6 by using the input voltage detection value vin, the output voltage detection value vo, and the reactor current iL, whereby the AC input current It has a PFC (Power Factor Correction) control function for controlling the input current iin after full-wave rectification so that iac has the same waveform and the same phase as the AC input voltage vac.
  • PFC Power Factor Correction
  • the target input current iin * which is a control target value for controlling the input current iin, has the same pulsating waveform with the same phase as the pulsating voltage
  • this can be adjusted by controlling the reactor current iL flowing through the reactor L of the converter 6.
  • power supply control unit 2 controls first and second switching elements Q1 and Q2 of converter 6 so that the average of reactor current iL per unit time matches target reactor current iL *.
  • FIG. 4 and 5 are circuit operation diagrams of step-up control and step-down control, respectively. 4 and 5, the horizontal axis indicates time, the waveform of the reactor current iL is shown on the upper side of the figure, and the operation waveforms of the first switching element Q1 and the second switching element Q2 are shown on the lower side of the figure. .
  • the first switching element Q1 and the first switching element Q1 are arranged so that the reactor current iL has a triangular shape between the upper limit target value iref * and the lower limit target value. 2 Controls the switching element Q2. The derivation of the upper limit target value iref * will be described later.
  • the first switching element Q1 is always turned on, the second switching element Q2 is turned on at the moment when the reactor current iL reaches the lower limit target value, and the reactor current iL becomes the upper limit target value iref *. At the moment of reaching, the second switching element Q2 is turned off.
  • the reactor current for boost control will be described with reference to FIG. FIG. 6 shows the path of the reactor current iL flowing through the converter 6 using arrows.
  • the first switching element Q1 is always on. Therefore, during the period when the second switching element Q2 is on, the reactor current iL flows through the path shown in FIG. 6A, and the pulsating voltage
  • the reactor current iL rises with a slope proportional to the pulsating voltage
  • the reactor current iL flows through the path shown in FIG. 6B, and the voltage difference (
  • the reactor current iL has a triangular waveform, and the target reactor current iL exceeds the target reactor current iL * by the amount that the reactor current iL exceeds the target reactor current iL *. Since the shortage of the reactor current iL that does not reach * is compensated, the average of the reactor current iL per unit time can be matched with the target reactor current iL *.
  • the second switching element Q2 is always turned off, the first switching element Q1 is turned on at the moment when the reactor current iL reaches the lower limit target value, and the reactor current iL becomes the upper limit target value iref *. At the moment of reaching, the first switching element Q1 is turned off.
  • the reactor current for step-down control will be described with reference to FIG. In the step-down control, since the second switching element Q2 is always turned off, the reactor current iL flows through the path shown in FIG. 6B during the period when the first switching element Q1 is on.
  • the reactor current iL It rises with a slope proportional to the voltage difference (
  • the reactor current iL flows through the path shown in FIG. 6C, and the output voltage ( ⁇ vdc) is applied to the reactor L. Therefore, the reactor current iL is added to the output voltage ( ⁇ vdc). Fall with a proportional slope.
  • the reactor current iL has a triangular waveform, and the target reactor current iL * is equivalent to the amount of the reactor current iL exceeding the target reactor current iL *. Since the shortage of reactor current iL that does not reach the value is compensated, the average of reactor current iL per unit time can be matched with target reactor current iL *.
  • the four-mode switching control includes a first mode in which both the first and second switching elements Q1, Q2 are in an on state, and a second mode in which the first switching element Q1 is in an on state and the second switching element Q2 is in an off state.
  • a third mode in which both the first and second switching elements Q1, Q2 are in an off state and a fourth mode in which the first switching element Q1 is in an off state and the second switching element Q2 is in an on state.
  • the reactor current iL is controlled to have a square waveform by turning on and off the first and second switching elements Q1 and Q2.
  • FIG. 7 is a circuit operation diagram of the four-mode switching control.
  • the horizontal axis indicates time
  • the waveform of the reactor current iL is shown on the upper side of the figure
  • the operation waveforms of the first switching element Q1 and the second switching element Q2 are shown on the lower side of the figure.
  • the first and second switching elements Q1 and Q2 are turned on / off so that the reactor current iL has a square waveform between the upper limit target value iref * and the lower limit target value.
  • the first switching element Q1 is turned on by a signal given to the first switching element Q1. Then, the first switching element Q1 is turned on and the second switching element Q2 is turned on, and operates in the first mode shown in FIG. In this first mode, reactor current iL flows through the path shown in FIG. 6A, and pulsating voltage
  • the first switching element Q1 is turned off by a signal given to the first switching element Q1. Then, the first switching element Q1 is turned off and the second switching element Q2 is turned off, and operates in the third mode shown in FIG.
  • the reactor current iL flows through the path shown in FIG. Since the output voltage ( ⁇ vdc) is applied to the reactor L, the reactor current iL falls with a slope proportional to the output voltage ( ⁇ vdc) as shown in a period T3 in FIG.
  • the converter 6 operates in four modes by operating the first and second switching elements Q1 and Q2 so as to overlap each other.
  • the reactor current iL has a rectangular waveform, and the shortage of the reactor current iL that does not reach the target reactor current iL * by the amount that the reactor current iL exceeds the target reactor current iL * is compensated. Therefore, the average of the reactor current iL per unit time can be matched with the target reactor current iL *.
  • the three-mode switching control includes a first mode in which both the first and second switching elements Q1, Q2 are in an on state, and a second mode in which the first switching element Q1 is in an on state and the second switching element Q2 is in an off state. And the first and second switching elements Q1 and Q2 are turned on and off so that the first mode and the second switching element Q1 and Q2 are in turn in the third mode. It is characterized by controlling to a rectangular waveform.
  • FIG. 8 is a circuit operation diagram of three-mode switching control.
  • the horizontal axis indicates time
  • the waveform of the reactor current iL is shown on the upper side of the figure
  • the operation waveforms of the first switching element Q1 and the second switching element Q2 are shown on the lower side of the figure.
  • the first switching element Q1 is turned off by a signal given to the first switching element Q1. Then, the first switching element Q1 is turned off and the second switching element Q2 is turned off, and operates in the third mode shown in FIG.
  • the reactor current iL flows through the path shown in FIG. Since the output voltage ( ⁇ vdc) is applied to the reactor L, the reactor current iL falls with a slope proportional to the output voltage ( ⁇ vdc) as shown in a period T3 in FIG.
  • the first and second switching elements Q1 and Q2 are turned on and off so that the reactor current iL has a rectangular waveform between the upper limit target value iref * and the lower limit target value.
  • the reactor current iL has a square waveform, and the shortage of the reactor current iL that does not reach the target reactor current iL * by the amount that the reactor current iL exceeds the target reactor current iL * is compensated. Therefore, the average of the reactor current iL per unit time can be matched with the target reactor current iL *.
  • the three-mode switching control can reduce the maximum value of the reactor current iL as compared with the four-mode switching control.
  • fixed frequency control which is one specific example of the multiple mode switching control according to the present embodiment.
  • a signal having a fixed frequency fQ1 and a fixed duty dQ1 is applied to the first switching element Q1, thereby turning on and off the first switching element Q1.
  • the second switching element Q2 is operated to turn on at the moment when the reactor current iL reaches the lower limit target value and to turn off at the moment when the reactor current iL reaches the upper limit target value iref *.
  • the reactor current waveform iL is a square waveform between the upper limit target value iref * and the lower limit target value.
  • fixed duty dQ1 is related to the maximum value of reactor current iL during fixed frequency control. That is, the maximum value of reactor current iL can be reduced by setting fixed duty dQ1 to a large value. As a result, the maximum value of the reactor current iL can be reduced as compared with the step-up / step-down control in the prior art, so that the loss generated in the reactor can be reduced. Thereby, the efficiency improvement as a power converter device is realizable.
  • the heat generated in the reactor can be reduced, it is possible to reduce the size of the reactor and the heat-dissipating component and thereby reduce the size of the device.
  • the setting of the above-described fixed duty dQ1 does not require detection of the input voltage or output voltage, and it is not necessary to change the value depending on the load or the magnitude of the input voltage.
  • the fixed frequency fQ1 of the signal given to the first switching element Q1 in the fixed frequency control will be described. It is desirable to set the fixed frequency fQ1 as small as possible from the viewpoint of reducing the switching loss.
  • the fixed frequency fQ1 is set using the resonance frequency of the input filter 4 so that the AC input current iac does not resonate at the resonance frequency determined by the input filter (LC filter) 4.
  • the switching frequency is lowered and approaches the resonance frequency of the input filter.
  • Switching of the step-down control is determined by the values of the pulsating voltage
  • the fixed frequency fQ1 may be set as the control switching frequency, and the operation may be switched to the fixed frequency control when the switching frequency of the step-up control or the step-down control becomes smaller than fQ1.
  • FIG. 9 is a diagram in which the configuration of the power supply control unit 2 of FIG. 2 is adapted to fixed frequency control.
  • symbol S means a process step.
  • the power supply control unit 2 When the control process is started, the power supply control unit 2 outputs the input voltage detection value vin obtained by detecting the pulsating voltage
  • Each of the detected output voltage values vo obtained by detecting the voltage vdc is fetched, and the target output voltage vo * indicating the control target value of the output voltage vdc is received from the host system (step S1).
  • the target output voltage vo * is received from the outside such as a host system, but is not limited to this, and may be a constant determined in advance in the power supply control unit 2.
  • the output control unit 21 outputs the output control amount i ** for controlling the output voltage vdc to a desired value by PI control (proportional integral control) from the deviation between the output voltage detection value vo and the target output voltage vo *. Is obtained (step S2).
  • PI control is used to calculate the control amount, but classical control such as PD control (proportional derivative control), PID control (proportional integral derivative control), or modern control H ⁇ control (H-infinity). Any control method may be used as long as it is a control method for bringing the error calculation result closer to the target value, such as control.
  • the comparison unit 22 compares the input voltage detection value vin (instantaneous value) with the magnitude of the output voltage detection value vo to obtain the upper limit target value iref *, and the current circuit operation of the power supply main circuit unit 1.
  • Step-up control, step-down control, fixed frequency control is determined (step S3). That is, the comparison unit 22 performs boost control when vin ⁇ vo, performs step-down control when vin> vo, and performs fixed frequency control when vin ⁇ vo.
  • Boosting control In the step-up control used when the input voltage detection value vin is smaller than the output voltage detection value vo (vin ⁇ vo), the common contact d of the first selector 23 connected to the output side of the output control unit 21 is connected individually to the step-up control side. The contact a is connected, and the individual contact a on the boost control side of the second selector 26d is connected to the common contact d.
  • PFC control is performed to control the input current iin after full-wave rectification so that the AC input current iac has substantially the same phase and waveform as the AC input voltage vac.
  • a target reactor current iL * is obtained.
  • the target reactor current iL * during the boost control can be set by the following equation (3) (step S4).
  • iL ** vin ⁇ i ** (3)
  • the target value calculation unit 24a sets the upper limit target value iref * by the following equation (4) using the above equation (1) and the above equation (3) (step S5).
  • the reactor current comparison unit 25a detects and takes in the reactor current iL from the current detection unit 7 of the power supply main circuit unit 1 (step S6). Then, the comparison is performed using the reactor current iL and the upper limit target value iref * obtained by the target value calculation unit 24a. Based on the comparison result, the switch control unit 26a generates and outputs a signal for controlling the first and second switching elements Q1 and Q2.
  • the first switching element Q1 is always turned on, and the second switching element Q2 is turned on at the moment when the reactor current iL reaches the lower limit target value (the lower limit target value is set to 0 here), Control is performed so that the second switching element Q2 is turned off at the moment when the reactor current iL reaches the upper limit target value iref * (step S7).
  • the above description is the control content of the power supply control unit 2 in the boost control.
  • Step-down control When the input voltage detection value vin is larger than the output voltage detection value vo (vin> vo) in the determination of step S3, step-down control is performed.
  • step-down control in FIG. 9, the common contact d of the first selector 23 connected to the output side of the output control unit 21 is connected to the individual contact b on the step-down control side, and each step-down control side of the second selector 26d. Are connected to the common contact d.
  • the target reactor current iL * at the time of step-down control can be set by the following equation (8) (step S8).
  • iL * ⁇ (vin) 2 / vo ⁇ ⁇ i ** (8)
  • the target value calculation unit 24b sets the upper limit target value iref * by the following equation (9) using the above equation (1) and the above equation (8) (step S9).
  • the reactor current comparison unit 25b detects and captures the reactor current iL from the current detection unit 7 of the power supply main circuit unit 1 (step S6). Then, the comparison is performed using the reactor current iL and the upper limit target value iref * obtained by the target value calculation unit 24b. Based on the comparison result, the switch control unit 26b generates and outputs a signal for controlling the first and second switching elements Q1 and Q2. That is, in step-down control, the second switching element Q2 is always turned off, and the first switching element Q1 is turned on at the moment when the reactor current iL reaches the lower limit target value (the lower limit target value is set to 0 here). The first switching element Q1 is controlled to be turned off at the moment when the target value iref * is reached (step S10).
  • the above description is the control content of the power supply control unit 2 in the step-down control.
  • the reactor current iL in the fixed frequency control is assumed as shown in FIG.
  • FIG. 11 shows a case where the period in which the reactor current iL rises and the period in which the reactor current iL rises are sufficiently short so that they can be ignored, and the pulsating voltage
  • vdc).
  • the reactor current iL flows only during the period when the first switching element Q1 is turned on, a current corresponding to the input current iin flows through the reactor L.
  • the reactor current iL having the magnitude of the upper limit target value iref * always flows during the period in which the first switching element Q1 is turned on, and the reactor current iL does not flow during the period in which the first switching element Q1 is turned off.
  • the relationship between the current iL * and the upper limit target value iref * is obtained using a fixed duty dQ1 of a signal applied to the first switching element Q1.
  • the target value calculation unit 24c sets the upper limit target value iref * by the following equation (10) using the fixed duty dQ1 of the signal applied to the first switching element Q1 and the above equation (3) (step S12).
  • the reactor current comparison unit 25c detects and captures the reactor current iL from the current detection unit 7 of the power supply main circuit unit 1 (step S6). Then, the comparison is performed using the reactor current iL and the upper limit target value iref * obtained by the target value calculation unit 24c. Based on the comparison result, the switch control unit 26c generates and outputs a signal for controlling the first and second switching elements Q1 and Q2. That is, in the fixed frequency control, a signal having a fixed frequency fQ1 and a fixed duty dQ1 is applied to the first switching element Q1 to perform an on / off operation, and the reactor current iL is a lower limit target value (the lower limit target value is set to 0 here).
  • the second switching element Q2 is controlled to be turned on at the moment when the value reaches the upper limit, and the second switching element Q2 is controlled to be turned off at the moment when the upper limit target value iref * is reached (step S13).
  • the above description is the control content of the power supply control unit 2 in the fixed frequency control.
  • the output control unit 21 the comparison unit 22, the selectors 23 and 26d, the target value calculation units 24a, 24b, and 24c, the reactor current comparison
  • the units 25a, 25b, 25c and the switch control units 26a, 26b, 26c are described in blocks for each function, but it is also possible to realize control of each function by a microcomputer using a control program. is there.
  • the loss generated in the reactor can be reduced by reducing the maximum value of the reactor current, the efficiency of the power converter can be improved. Moreover, since the heat generated in the reactor is reduced, it is possible to reduce the size of the reactor and the heat dissipating component and thereby reduce the size of the power converter.
  • the fixed duty dQ1 can be further increased, and the first switching element Q1 can be set to be turned on at the timing when the reactor current iL reaches the lower limit target value.
  • the three-mode switching control described above is performed. By operating the first and second switching elements Q1, Q2 by the three-mode switching control, the maximum value of the reactor current can be further reduced.
  • the first switching element Q1 or the second switching element Q2 is turned on at the timing when the reactor current iL reaches the lower limit target value.
  • the lower limit target value is preferably set to zero (0) in order to reduce the switching loss generated in the first and second switching elements Q1 and Q2. In the above description, the lower limit target value is set to zero. Explained the case.
  • the lower limit target value is not limited to zero (0), and may be set to a value other than zero (0).
  • the difference between the upper limit target value and the lower limit target value is reduced by setting the lower limit target value to a value larger than zero (0), and the reactor current iL Therefore, the ripple of the current output from the converter 6 can be reduced.
  • the first switching element Q1 is supplied with a signal having the fixed frequency fQ1 and the fixed duty dQ1 to turn on and off the first switching element Q1, and the reactor current iL is applied to the second switching element Q2. Is turned on at the moment when the value reaches the lower limit target value, and is turned off at the moment when the upper limit target value iref * is reached, so that the reactor current waveform iL has a rectangular shape between the upper limit target value iref * and the lower limit target value.
  • the waveform can be controlled.
  • any control method other than those described above may be applied as long as the on / off operation of the first and second switching elements Q1 and Q2 is controlled in a plurality of modes to control the reactor current iL to a square waveform. May be.
  • PWM Pulse Width Modulation
  • 12 shows the comparison between the triangular wave and the comparison value
  • the middle part of FIG. 12 shows the on / off operation of the first and second switching elements Q1 and Q2
  • the lower part of FIG. 12 shows the waveform of the reactor current.
  • two triangular waves having different phases of the first triangular wave TW1 and the second triangular wave TW2 are prepared.
  • the first triangular wave TW1 is used for the on / off operation of the first switching element Q1, and the second triangular wave TW2 is Used for the on / off operation of the second switching element Q2.
  • the first switching element Q1 compares the first triangular wave TW1 with the comparison value RW, turns on when the first triangular wave TW1 is larger than the comparison value RW, and turns off when the first triangular wave TW1 is smaller than the comparison value RW.
  • the second switching element Q2 compares the second triangular wave TW2 with the comparison value RW, turns on when the second triangular wave TW2 is larger than the comparison value RW, and turns off when the second triangular wave TW2 is smaller than the comparison value RW.
  • the reactor current iL can be controlled to have a square waveform as shown in the lower part of FIG.
  • the power supply control unit 2 controls the converter 6 in step-up control, step-down control, and multiple mode switching control based on a comparison between the input voltage, that is, the input voltage detection value vin, and the output voltage, that is, the output voltage detection value vo. It was made to switch and operate between. However, it is not necessary to combine all of the above three controls (step-up control, step-down control, and multi-mode switching control). For example, the combination of step-up control and multi-mode switching control or step-down control and multi-mode switching control. These two controls may be combined. Further, the multi-mode switching control may always be performed regardless of the difference between the input voltage and the output voltage.
  • the power supply control unit 2 when performing the fixed frequency control as the multi-mode switching control, the power supply control unit 2 always turns on the first switching element Q1 and sets the second switching element Q2 to the reactor current based on the comparison between the input voltage and the output voltage.
  • Step-up control that turns off when iL reaches the upper limit target value iref *, and turns on when the reactor current iL reaches the lower limit target value, and always turns off the second switching element Q2, and sets the reactor current iL to the upper limit of the first switching element Q1. If the converter 6 is operated by combining at least one of the step-down control to be turned off when the target value iref * reaches the target value iref * and turned on when the reactor current iL reaches the lower limit target value, and the fixed frequency control. good.
  • the fixed frequency control may always be performed regardless of the difference between the input voltage and the output voltage.
  • the input current waveform is changed to the input voltage waveform while the reactor current is controlled to the square waveform by operating the H-bridge type buck-boost converter by the multi-mode switching control.
  • the power factor can be improved so as to approximate the same phase and waveform.
  • the reactor current can be controlled into a square waveform, the maximum value of the reactor current can be reduced, and the loss generated in the reactor can be reduced. For this reason, it is possible to realize high efficiency of the power conversion device, and it is possible to reduce the size of the power conversion device due to the miniaturization of the reactor and the heat dissipation component.
  • the maximum value of the reactor current can be greatly reduced by performing the three-mode switching control as the multi-mode switching control.
  • the first switching element is turned on / off by a signal having a fixed frequency and a fixed duty, and the second switching element is turned off when the reactor current reaches the upper limit target value, so that the reactor current becomes the lower limit target.
  • the reactor current can be controlled to a square waveform, and the maximum value of the reactor current can be reduced to reduce the loss generated in the reactor. it can.
  • the fixed frequency control can be realized with a simple arithmetic expression.
  • the fixed duty of the first switching element used in the fixed frequency control so as to reduce the maximum value of the reactor current
  • the maximum value of the reactor current can be further reduced, and the loss generated in the reactor can be reduced. Can be reduced.
  • the upper limit target value in the fixed frequency control can be set to be lower than the upper limit target value in the boost control, and the maximum value of the reactor current during the fixed frequency control is reduced. be able to.
  • a combination of step-up control for boosting the H-bridge type buck-boost converter, step-down control for stepping down the H-bridge type buck-boost converter, and multiple mode switching control is combined.
  • the target output voltage can be realized regardless of the magnitude of the input voltage.
  • any one of the step-up control for boosting the H-bridge type buck-boost converter and the step-down control for stepping down the H-bridge type buck-boost converter may be combined to operate the H-bridge type buck-boost converter.
  • the first switching element is always turned on, and the second switching element is turned off when the reactor current reaches the upper limit target value, and turned on when the reactor current reaches the lower limit target value.
  • Step-up control, step-down control that always turns off the second switching element, turns off the first switching element when the reactor current reaches the upper limit target value, and turns on when the reactor current reaches the lower limit target value; fixed frequency control;
  • the first switching element is always turned on, and the second switching element is turned off when the reactor current reaches the upper limit target value, and turned on when the reactor current reaches the lower limit target value.
  • One control and fixed frequency control may be combined to operate the H-bridge type buck-boost converter.
  • the first and second switching elements are turned on when the reactor current iL is at the lower limit target value (0). Switching loss generated in the two switching elements can be reduced, and high efficiency of the power conversion device can be realized.
  • the power conversion device according to the first embodiment is configured by a single-stage converter and performs control using a comparison result of the reactor current, the upper limit target value, and the lower limit target value, the number of parts is small and the cost is low. In addition, a highly efficient power conversion device can be realized.
  • FIG. FIG. 13 is a circuit block diagram showing the configuration of the power supply control unit of the power conversion device according to the second embodiment of the present invention. Components identical or corresponding to those in FIG. 2 or FIG. Is attached.
  • the configuration of power supply main circuit unit 1 of the power conversion device according to the second embodiment is the same as that of FIG. 1 of the first embodiment.
  • the arithmetic expression (10) of the upper limit target value iref * at the time of fixed frequency control is obtained when the input voltage and the output voltage are substantially equal (
  • the calculation formula of the upper limit target value iref * at the time of fixed frequency control is changed with respect to the first embodiment, and the fixed frequency control is used when a difference occurs between the input voltage and the output voltage.
  • An arithmetic expression of a suitable upper limit target value iref * is provided.
  • FIG. 14 shows the waveform of reactor current iL considered in the second embodiment.
  • the period in which the reactor current iL rises and the period in which the reactor current iL rises are approximated to 0, as in FIG. 11.
  • the first switching element Q1 is on and the second switching element Q2 is off.
  • the reactor current iL has a waveform with a slope proportional to the voltage difference (
  • the target reactor current iL * is obtained by using an upper limit target value iref *, an input voltage detection value vin, an output voltage detection value vo, a fixed frequency fQ1 and a fixed duty dQ1 of a signal applied to the first switching element Q1, and an inductance L of the reactor L. It is calculated as equation (11).
  • iL * iref * ⁇ dQ1 + ⁇ (vin ⁇ vo) ⁇ (dQ1) 2 / (2 ⁇ L ⁇ fQ1) ⁇ (11)
  • the target value calculation unit 24c sets the upper limit target value iref * by the following equation (12) using the above equation (3) and the above equation (11).
  • iref * (vin ⁇ i ** / dQ1) ⁇ ⁇ (vin ⁇ vo) ⁇ dQ1 / (2 ⁇ L ⁇ fQ1) ⁇ (12)
  • Equation (12) The first term on the right side of Equation (12) is the same as the right side of Equation (10), and the second term on the right side of Equation (12) is a term proportional to the above-described input / output voltage difference (vin ⁇ vo). . That is, the right side of Expression (12) depends on the input / output voltage difference (vin ⁇ vo) shown in the white area portion SA2 in FIG. 14 for a term that does not depend on the input / output voltage difference shown in the hatched area portion SA1 in FIG. The equation is corrected by the term.
  • the upper limit target value used in the fixed frequency control is a value proportional to the input voltage divided by the fixed duty of the first switching element. Since the corrected value is set according to the value proportional to the voltage difference, the power factor is improved without causing distortion in the AC input current even if there is a difference between the input voltage and the output voltage. be able to.
  • the second embodiment is intended to prevent power factor reduction and non-compliance with harmonic standards caused by an error in the calculated value of the upper limit target value when a high power factor is required.
  • the AC input current can be converted to AC input voltage without causing distortion in the AC input current by calculating the upper limit target value as Equation (12).
  • the power factor can be improved with the same phase and waveform.
  • FIG. 15 and 16 are circuit block diagrams showing a power supply main circuit unit and a power supply control unit of a power conversion device according to Embodiment 3 of the present invention. Components identical or corresponding to those in Embodiment 1 are designated by the same reference numerals. Is attached.
  • the load 10 is an LED unit in which a plurality of LEDs (Light Emitting Diodes) are connected in series on the premise of the power conversion device shown in the first embodiment.
  • the connection method of LED of the LED unit used as the load 10 is not limited to simply connecting in series, and may be parallel connection or series-parallel connection, or may be a single LED.
  • the LED current detection part 11 is added as a detection circuit for detecting the LED current iLED which flows into LED with respect to the circuit structure of Embodiment 1.
  • the LED current iLED and the target output current iLED * detected by the LED current detection unit 11 are input.
  • the target value calculation unit 24c at the time of fixed frequency control in FIG. 16 uses the equation (10) obtained in the first embodiment, the equation (12) obtained in the second embodiment is used as the target value calculation unit 24c. May be used.
  • the LED current iLED flowing through the LED can be controlled by the same control as in the first and second embodiments.
  • the dimming function can also be realized if the above-described target output current iLED * is made variable from an external device.
  • the LED current detected by the LED current detection unit is fed back to the power supply control unit, and the LED is detected by the output control unit. Control is performed so that the current becomes the target output current. Then, by performing on / off control of the first and second switching elements by the target value calculation unit, the reactor current comparison unit, and the switch control unit described in the first embodiment, low-cost, high power factor, high-efficiency power conversion can be performed. Can be achieved.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Rectifiers (AREA)

Abstract

Selon la présente invention, une unité de commande de puissance (2) effectue une commande de commutation multimode qui met en marche et en arrêt des premier et second éléments de commutation (Q1, Q2) dans un convertisseur élévateur/abaisseur de type à pont en H (6) de sorte que le convertisseur élévateur/abaisseur de type à pont en H présente, dans l'ordre suivant : un premier mode dans lequel à la fois les premier et second éléments de commutation (Q1, Q2) sont dans un état MARCHE ; un deuxième mode dans lequel le premier élément de commutation (Q1) est dans l'état MARCHE et le second élément de commutation (Q2) est dans un état ARRÊT ; et un troisième mode dans lequel à la fois les premier et second éléments de commutation (Q1, Q2) sont dans l'état ARRÊT.
PCT/JP2016/087215 2016-12-14 2016-12-14 Dispositif de conversion de puissance WO2018109864A1 (fr)

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JP7404666B2 (ja) 2019-06-11 2023-12-26 富士電機株式会社 集積回路、電源回路

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