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WO2018131748A1 - Appareil de modulation de signal de fréquence sans fil - Google Patents

Appareil de modulation de signal de fréquence sans fil Download PDF

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Publication number
WO2018131748A1
WO2018131748A1 PCT/KR2017/001954 KR2017001954W WO2018131748A1 WO 2018131748 A1 WO2018131748 A1 WO 2018131748A1 KR 2017001954 W KR2017001954 W KR 2017001954W WO 2018131748 A1 WO2018131748 A1 WO 2018131748A1
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WO
WIPO (PCT)
Prior art keywords
coupler
capacitors
switched
combiner
port
Prior art date
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PCT/KR2017/001954
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English (en)
Korean (ko)
Inventor
홍성철
강승훈
김기철
Original Assignee
한국과학기술원
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
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Priority claimed from KR1020170019402A external-priority patent/KR102002787B1/ko
Application filed by 한국과학기술원 filed Critical 한국과학기술원
Publication of WO2018131748A1 publication Critical patent/WO2018131748A1/fr

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/36—Modulator circuits; Transmitter circuits

Definitions

  • the present invention relates to a radio frequency signal modulation device.
  • the transmitter of the conventional in-phase and quadature-phase signaling methods has a structure as shown in FIG.
  • the I / Q transmitter receives in-phase (I) and quadature-phase (Q) signals from the digital signal section at the front end, and the digital to analog converter (DAC), low pass filter (LPF), mixer in each signal path.
  • the baseband signal is up-converted to a signal of a desired band through a mixer, and a desired radio frequency signal is generated by a vector sum of modulated I and Q signals.
  • this conventional I / Q scheme not only has a large number of components constituting the transmitting end, but also provides a calibration to compensate for mismatches between corresponding components between I and Q signal paths.
  • the disadvantage is that the required time is longer and more difficult. This is expected to incur a lot of cost in implementing the massive multiple input, multiple output (MIMO) transceiver that is proposed as the core of the next generation communication.
  • MIMO massive multiple input, multiple output
  • each component is basically fixed in the operating band frequency characteristics, it is difficult to support the recently required multi-mode and multi-band. Therefore, in order to minimize the cost of a transceiver in a massive MIMO transmission / reception environment, new transmitter structures that are advantageous for minimizing the number of components required for the transmitter and supporting multimode and multiband have been studied.
  • a six-port RF modulator can essentially combine the two quadrature signals into a Wilkinson combiner to produce the desired RF signal.
  • a desired radio frequency signal as shown in Equation 1 below.
  • the 6-port RF modulator can be expressed by the reflection coefficient value generated from the impedance of the output port.
  • Quadrature couplers constituting a 6-port radio frequency signal modulator may use quadrature hybrid couplers (branch line couplers).
  • the coupler disclosed in FIG. 3 is a representative microstrip / stripline coupler using direct coupling through a branch line.
  • the two outputs are half and half power, that is, -3 dB coupler. It distributes evenly and two equal output signals have a phase difference of 90 degrees.
  • the power combiner constituting the 6-port RF signal modulator may use a Wilkinson power combiner as shown in FIG. 4.
  • Wilkinson power combiners are bidirectional and can be used as a hybrid of combiners or dividers. Applying power to an input port with a 50 ohm characteristic impedance results in an output with 50 ohms characteristic impedance with twice the power as the output port.
  • quadrature hybrid coupler and Wilkinson power combiner constituting this 6-port RF modulator have ⁇ / 4 corresponding to 4cm at 2GHz, they cannot be integrated inside the chip and must be implemented in the form of microstrip line on the printed circuit board. do.
  • the 6-port radio frequency signal modulator consists of passive components only and is a new transmitter structure suitable for the development direction of the system.
  • the 6-port RF signal modulator technology which has been advanced to date, has been difficult to realize the multiband concept ultimately pursued by the 6-port RF signal modulator due to the narrowband characteristics of the coupler and combiner.
  • FIGS. 5 and 6 disclose a quadrature hybrid coupler and Wilkinson power combiner applied to a lumped-element circuit.
  • a lumped-element quadrature hybrid coupler consisting of an inductor and a capacitor and a lumped-element Wilkinson power combiner consisting of an inductor capacitor resistor have the advantage of simple integration inside the chip because there is no ⁇ / 4.
  • the coupler disclosed in FIGS. 5 and 6, like the coupler and the combiner including the electric branch line, has a big disadvantage in that it has a narrow band characteristic.
  • An object of the present invention is to provide a multi-band radio frequency signal modulation apparatus compatible at a wide band frequency including low band and high band.
  • the present invention is a radio frequency signal modulation apparatus using 6 ports in a lumped-element circuit, the phase difference inverted by receiving a signal of a local oscillator (LO)
  • a first coupler for outputting two signals having a quadrature and an orthogonality of the two output signals
  • a second coupler configured to convert a magnitude of a signal divided by the first coupler by adjusting a load of the output terminal
  • a combiner configured to vector-add two signals converted from the second coupler and output a radio frequency to an output port, wherein the first coupler and the second coupler are composed of a plurality of capacitors and inductors, and the capacitor is a switched capacitor. do.
  • a plurality of second couplers may be provided to separately receive the two signals outputted by the phase difference inverted by the first coupler.
  • the first coupler and the second coupler may be a Lange coupler configured to bend the track.
  • the first coupler and the second coupler may have a plurality of switched capacitors connected in parallel.
  • the first coupler and the second coupler may be switched inductors.
  • the combiner consists of a plurality of capacitors and the capacitor may be a switched capacitor.
  • a plurality of switched capacitors may be connected in parallel.
  • the combiner is composed of a plurality of inductors and the inductor may be a switched inductor.
  • a multi-band radio frequency signal modulation device using a switched capacitor can be realized by miniaturizing it with a CMOS IC chip with the advantage of simplicity and low power consumption through a 6-port structure, and not a single frequency.
  • the advantage is that it can be applied to ultra-wide bandwidth.
  • the proposed RF signal modulation apparatus can be used as a new transmission structure in a multiband next generation MIMO communication system.
  • FIG. 3 shows a quadrature hybrid coupler for a conventional 6-port RF signal modulator.
  • FIG. 4 shows a Wilkinson power combiner for a conventional 6-port RF signal modulator.
  • FIG. 5 shows a lumped-element quadrature hybrid coupler for a conventional 6-port RF signal modulator.
  • FIG. 6 shows a lumped-element Wilkinson power combiner for a conventional 6-port RF signal modulator.
  • FIG. 7 is a circuit diagram of a radio frequency signal modulation device according to an embodiment of the present invention.
  • FIG. 8 is a schematic diagram showing the structure and operation of a switched capacitor according to an embodiment of the present invention.
  • FIG. 9 shows a first coupler according to an embodiment of the invention.
  • FIG. 10 shows a second coupler according to an embodiment of the invention.
  • FIG. 11 illustrates a combiner according to an embodiment of the present invention.
  • FIG. 12 is a circuit diagram of a radio frequency signal modulation device in which two of the capacitors of each coupler are tuned according to an embodiment of the present invention.
  • FIG. 13 is a circuit diagram of a radio frequency signal modulation apparatus tuned using a range coupler according to an embodiment of the present invention.
  • FIG. 14 is a circuit diagram of a radio frequency signal modulation device implemented with a multi-band according to an embodiment of the present invention.
  • 15 is a circuit diagram of a radio frequency signal modulation apparatus in which a capacitor and an inductor are tuned according to an embodiment of the present invention.
  • FIG. 16 shows a signal modulation result of the radio frequency signal modulation device according to an embodiment of the present invention.
  • 17 shows a result of comparing the modulation result of the radio frequency signal modulation device according to an embodiment of the present invention with the result of the conventional device.
  • FIG. 18 is a diagram of an actual radio frequency signal modulation apparatus according to an embodiment of the present invention.
  • the radio frequency signal modulation device 1 basically has a capacitor constituting a coupler (hereinafter, coupler) and combiner (hereinafter, a combiner) used in a conventional lumped-element circuit.
  • Switched capacitors (110, 130, 150) can be changed to operate at a wide frequency instead of one band each.
  • the capacitance values of the switched capacitors 110, 130, and 150 may have a large capacitance value in a low band and a small capacitance value in a high band.
  • the radio frequency signal modulation device 1 is composed of a 6-port and may be implemented in a circuit structure including a first coupler 11, a second coupler 13, and a combiner 15.
  • FIG. 8 is a schematic diagram showing the structure and operation of the switched capacitor (110, 130, 150) according to an embodiment of the present invention.
  • the switched capacitors 110, 130, and 150 need to be activated to have high capacitance values in the low band.
  • the switch can be implemented as a simple transistor and can produce an operation in which the switch is activated by applying a gate bias (Vg) at a high voltage. Conversely, to have low capacitance in the high band, Vg can be applied at low voltage and the switch can be deactivated.
  • Vg gate bias
  • the first coupler 11 may receive a local oscillator (LO) signal 3 and output two signals having inverted phase differences to ensure orthogonality of the output two signals.
  • LO local oscillator
  • the first coupler 11 may include an input port 111, a direct port 113, a coupled port 115, and an isolated port 117.
  • the first coupler 11 may receive the local oscillator signal 3 through the input port 111.
  • the first coupler 11 may evenly output the received signal to the direct port 113 and the coupled port 115 to have a size of -3 dB.
  • the first coupler 11 may ensure orthogonality between the two signals by having a phase difference of 90 degrees with respect to the signals output from the direct port 113 and the coupled port 115 regardless of the frequency of the input signal.
  • the isolated port 117 of the first coupler 11 may be grounded by resistive ground in accordance with the line impedance to be interrupted and thus not actually used for input / output.
  • the isolated port 117 has a function of grounding with a resistor so as not to be reflected back to the leakage power because the power is not transmitted structurally to induce heat to stabilize the coupler.
  • the couplers 11 and 13 and the combiner 15 may include a plurality of capacitors and an inductor. All or part of the capacitors constituting the couplers 11 and 13 may be selectively tuned.
  • the first coupler 11 may improve the circuit integration of the first coupler 11 by tuning all or part of the capacitors constituting the first coupler 11 to the switched capacitor 110.
  • the first coupler 11 may include a plurality of capacitors. 7 to 15, the first coupler 11 may include six capacitors. Define the capacitor located in the upper right corner as C1, and define each capacitor listed clockwise as C6. The first coupler 11 may select a capacitor that is tuned to be implemented in a miniaturized state while generating a phase difference between signals output to the direct port 113 and the coupled port 115.
  • the first coupler 11 may tune four capacitors.
  • C1, C3, C4, and C6 may be tuned to the switched capacitor 110 in the first coupler 11.
  • other tuning methods may be sought to improve the integration of the circuit.
  • the first coupler 11 tunes two capacitors to output two signals having a phase difference of 90 degrees, and may be implemented in a miniaturized state to be integrated in the chip. That is, C2 and C5 of the first coupler 11 may be tuned to the switched capacitor 110. As a result, the degree of integration of the circuit may be improved compared to the case where the four capacitors are tuned.
  • the capacitors are tuned in symmetrical positions so that the path of the circuit can be maintained so that the first coupler 11 can output two signals having a phase difference of 90 degrees. have.
  • tuning of the inductor is not included, and tuning of the inductor may be added to extend the frequency range utilized.
  • FIG. 13 is a circuit diagram of a radio frequency signal modulation device 1 tuned using a Lange coupler 114, 134 according to an embodiment of the present invention.
  • the RF signal modulation apparatus 1 may tune the first coupler 11 or the second coupler 13 to range couplers 114 and 134.
  • the range coupler is a pod-type microstrip coupler composed of staggered microstrip lines, and is used as an attenuator, balance amplifier, balanced antenna feed element, RF amplifier, mixer, combiner, and divider.
  • the range coupler is a power distribution coupler considering the wavelength relationship, but is smaller in size than other couplers because it is formed in a bent line. Therefore, since the range coupler is easy to be mounted inside a high frequency semiconductor of over 10 GHz, it is used for power distribution of high frequency integrated circuits.
  • the first coupler 11 may be a range coupler 114 configured to have a curved line.
  • the first coupler 11 may be composed of a range coupler 114 having a smaller size than other couplers, and thus may be easily integrated into the chip.
  • the first coupler 11 may extend the bandwidth in each band by using the range coupler 114 instead of the quadrature hybrid coupler (branch line coupler). That is, the first coupler 11 may include the range coupler 114 to not only utilize a wide frequency but also to be miniaturized and integrated into a chip.
  • the RF signal modulation apparatus 1 may include a structure in which the switched capacitors 110, 130, and 150 are connected in parallel.
  • a plurality of switched capacitors 110 may be connected in parallel.
  • the first capacitor 11 may be connected to the switched capacitor 110 in parallel in the tuning process of the capacitor.
  • dual bands for high frequency and low frequency single bands may be implemented.
  • multiple bands of dual bands or more may be implemented at high and low frequencies. Accordingly, the first coupler 11 may output a signal at a wide frequency.
  • the first coupler 11, the second coupler 13, and the combiner 15 may use a switched inductor 112.
  • the inductor of the first coupler 11 may be a switched inductor 112.
  • the first coupler 11 may include a plurality of inductors.
  • the inductors provided in the plurality of first couplers 11 an inductor located at a relatively upper end is defined as L1, and an inductor located at a lower end is defined as L2.
  • the first coupler 11 tuned the capacitors C1 to C6.
  • the inductor may be tuned to the switched inductor 112.
  • the first coupler 11 may tune both the L1 and L2 inductors to the switched inductors 112 to implement the dual band.
  • the user may tune the capacitor to the switched capacitor 110, and by tuning the even number of capacitors in the symmetrical position, multiple bands of dual bands or more may be implemented.
  • the first coupler 11 may use the switched inductor 112 to select a frequency through the circuit.
  • the first coupler 11 may reduce the inductance of the switched inductor 112 when the frequency of the high frequency band passes.
  • the inductance of the switched inductor 112 may be increased.
  • the selectable frequency domain range may be improved. In detail, through the configuration of the switched inductor 112, the frequency can be efficiently selected regardless of the light weight of the load.
  • the second coupler 13 may convert a magnitude of a signal divided by the first coupler 11 by adjusting a load of an output terminal.
  • the second coupler 13 may include an input port 131, a direct port 133, a coupled port 135, and an isolated port 137.
  • the direct port 133 and the coupled port 135 may constitute an output terminal.
  • the second coupler 13 may adjust the load of the direct port 133 and the coupled port 135.
  • the direct port 133 and the coupled port 135 of the second coupler 13 may be connected to the rod modulator. Through this, the second coupler 13 may adjust the magnitude of the signal received from the first coupler 11.
  • the second coupler 13 may transmit the scaled signal to the combiner 15 through the isolated port 137.
  • the second coupler 13 may be provided in plural to separately receive two signals output by the phase difference inverted by the first coupler 11.
  • the second coupler 13 couples the respective signals 3a and 3b having the phase difference of 90 degrees to the direct port 113 and the coupled port 113 of the first coupler 11. Received through each of the (115).
  • the second coupler 13a may receive a signal 3a output from the direct port 113 of the first coupler 11.
  • the second coupler 13b may receive a signal 3b output from the coupled port 115 of the first coupler 11.
  • each of the second couplers 13a and 13b receives the different signals 3a and 3b having the phase difference, converts the magnitudes, and transfers the magnitudes to the combiner 15.
  • the second coupler 13 tunes all or some of the capacitors constituting the second coupler 13 to the switched capacitor 130 to improve the circuit density of the second coupler 13. You can.
  • the second couplers 13a and 13b may include a plurality of capacitors. 7 to 15, the second couplers 13a and 13b may include six capacitors.
  • the capacitor located on the upper right side of the second coupler 13a is defined as C1a, and each capacitor listed in the clockwise direction is sequentially defined as C6a.
  • the capacitor located at the upper right of the second coupler 13b is defined as C1b, and each capacitor listed in the clockwise direction is sequentially defined as C6b.
  • the second couplers 13a and 13b may select a capacitor tuned to convert a signal output to the isolated port 137 while adjusting the load applied to the direct port 133 and the coupled port 135.
  • the second couplers 13a and 13b may tune four capacitors.
  • C1a (b), C3a (b), C4a (b), and C6a (b) may be tuned to the switched capacitor 130 in the second couplers 13a and 13b.
  • other tuning methods may be sought to improve the integration of the circuit.
  • the second couplers 13a and 13b may be integrated into the chip by tuning the two capacitors to the switched capacitor 13. That is, C2a (b) and C5a (b) of the second couplers 13a and 13b may be tuned to the switched capacitor 130. As a result, the degree of integration of the circuit may be improved compared to the case where the four capacitors are tuned.
  • the capacitors when two or four switched capacitors 130 are applied, the capacitors may be tuned to left and right symmetric positions.
  • tuning of the inductor when the above-described switched capacitor 130 is applied, tuning of the inductor is not included, and tuning of the inductor may be added to extend the frequency range utilized.
  • the second coupler 13 may be a range coupler 134 configured to have a curved line.
  • the second coupler 13 may be composed of a range coupler 134 having a smaller size than other couplers, and thus may be easily integrated into the chip.
  • the second coupler 13 may extend the bandwidth in each band by using the range coupler 134 instead of the quadrature hybrid coupler (branch line coupler).
  • the second coupler 13 may include the range coupler 134 to not only utilize a wide frequency but also to be miniaturized and integrated into a chip.
  • a plurality of switched capacitors 130 may be connected in parallel.
  • the second coupler 13 may be connected to the switched capacitor 130 in parallel during the tuning of the capacitor.
  • dual bands for high frequency and low frequency single bands may be implemented.
  • multiple bands of dual bands or more may be implemented at high and low frequencies.
  • the inductor of the second coupler 13 may be a switched inductor 132.
  • the second coupler 13 may include a plurality of inductors.
  • the inductor located at the upper end is defined as L1a (b)
  • the inductor located at the lower end is defined as L2a (b).
  • the second couplers 13a and 13b tuned the capacitors C1a (b) to C6a (b).
  • the inductor of the circuit may be tuned to the switched inductor 132.
  • the second coupler 13 may tune both the L1a (b) and L2a (b) inductors to the switched inductors 132 to implement the dual band. In this case, the user may tune the capacitor to the switched capacitor 130 and may tune an even number of capacitors in a symmetrical position.
  • the second coupler 13 may use the switched inductor 132 to select a frequency through the circuit.
  • the second coupler 13 may reduce the inductance of the switched inductor 132 when the frequency of the high frequency band passes.
  • the inductance of the switched inductor 132 may be increased.
  • the selectable frequency domain range may be improved. In detail, through the configuration of the switched inductor 132, the frequency can be efficiently selected regardless of the light weight of the load.
  • the combiner 15 may output the radio frequency 5 to the output port 155 by summing two signals converted by the second coupler 13.
  • the combiner 15 may include a plurality of input ports 151 and 153 and output ports 155.
  • the combiner 15 may receive two different signals whose sizes are changed by the second couplers 13a and 13b through respective input ports 151 and 153.
  • the combiner 15 may vector-add each input signal and output the combined signal to the output port 155.
  • the signal output through the combiner 15 may be a radio frequency (5) signal.
  • the combiner 15 may be composed of a plurality of capacitors, and the capacitor may be a switched capacitor 150.
  • the combiner 15 may include a plurality of capacitors.
  • the combiner 15 may include four capacitors.
  • the capacitor located in the upper right corner is defined as C1c, and each capacitor listed in the clockwise direction is sequentially defined as C2c, C3c, and C4c.
  • the combiner 15 receives the respective signals from the two second couplers 13a and 13b through different input ports 151 and 153 and sums them together, and outputs them by combining the capacitors.
  • the combiner 15 switches the capacitors to be miniaturized. Can be tuned to 150.
  • the combiner 15 is limited to four capacitors provided unlike the coupler, so that positions for satisfying both the left, right, and top and bottom symmetry on the circuit may be limited when all capacitors are tuned. Accordingly, when the capacitors of C1c to C4c are tuned, the wideband frequency may be utilized, and the degree of integration of the circuit may be improved.
  • tuning of the inductor is not included, and tuning of the inductor may be added to extend the frequency range utilized.
  • a plurality of switched capacitors 150 may be connected in parallel.
  • the combiner 15 may have a plurality of switched capacitors 150 connected in parallel during the tuning of the capacitors.
  • a single number of switched capacitors 150 is applied to the combiner 15, dual bands for high frequency and low frequency single bands may be implemented.
  • the switched capacitors 150 are connected in parallel, multiple bands of dual bands or more may be implemented at high and low frequencies.
  • the combiner 15 may be composed of a plurality of inductors and the inductor may be a switched inductor 152.
  • the combiner 15 may include a plurality of inductors.
  • the inductor located at the upper end is defined as L1c and the inductor located at the lower end is defined as L2c.
  • the combiner 15 tuned the capacitors C1c to C4c.
  • the inductor can be tuned to the switched inductor 152.
  • the combiner 15 may tune both L1c and L2c inductors to the switched inductor 152. In this case, the user may tune the capacitor to the switched capacitor 150.
  • the combiner 15 may use a switched inductor 152 to select frequencies through the circuit.
  • the combiner 15 may reduce the inductance of the switched inductor 152 when the frequency of the high frequency band passes.
  • the inductance of the switched inductor 152 may be increased.
  • the selectable frequency domain range may be improved. In detail, through the configuration of the switched inductor 152, the frequency can be efficiently selected regardless of the light weight of the load.
  • the combiner 15 has two input ports 151 and 153 unlike the coupler.
  • additional configuration may be required to isolate the two input ports 151, 153.
  • Such a configuration may be defined as a resistor connecting the input ports 151 and 153. If the two input ports 151 and 153 are not isolated through a resistor, each signal input to the combiner 15 may be transmitted to a different input port. That is, a signal output through the second coupler 13a and input to the input port 151 directly passes to the input port 153, or similarly, is output through the second coupler 13b to the input port 153. The input signal may be immediately passed to the input port 151.
  • FIG. 16 shows modulation results of the radio frequency 5 signal in each band (low band / high band) through the modulation operation.
  • high-tunable capacitance can be used to obtain a square frequency modulated quadrature modulus (16QAM) signal, and in the high band, low-tunable capacitance can also be modulated in square 16QAM 5) A signal can be obtained.
  • the rotation of the formed constellation for each frequency may be operable in the digital unit in front of the radio frequency signal modulation device. It is important to note that the focus here is on how to maintain a uniform square shape.
  • the bandwidth may be extended in each band by using a Lange coupler rather than a quadrature hybrid coupler (branch line coupler).
  • a uniform modulated radio frequency (5) signal can be obtained in the low band of 1.6 GHz to 2.0 GHz and in the high band of 2.2 GHz to 2.6 GHz.
  • the result is a direct implementation. In other words, note that the result is not a theoretically calculated result but a result actually implemented inside the chip.
  • an ultra-wideband 6port radio frequency signal modulation device 1 can be implemented using a wide-range Lange coupler and a dual band implementation using tunable capacitance from 1.6 GHz to 2.6 GHz.
  • the radio frequency signal modulation device 1 is integrated inside the chip in a size of 1.9 mm x 0.9 mm. Through this, it is possible to bring about tens of times the size reduction compared to the 6-port signal modulation device implemented on the PCB by the size of several cm, and the switched capacitors 110, 130, and 150 for implementing the multi-band also have a small size Can be. In addition, it is possible to further minimize the size by inserting the switched capacitors (110, 130, 150) in the Lange coupler.
  • Radio frequency signal modulation apparatus can be implemented by miniaturizing the CMOS chip by using a Lange coupler, a switched capacitor and a switched inductor, and has the advantages of simplicity of structure and low power consumption. It has the advantage that it can be applied to ultra-wideband instead of frequency. Therefore, the RF signal modulation apparatus can be used as a new transmission structure in the next generation MIMO communication system.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Transmitters (AREA)

Abstract

La présente invention concerne un appareil de modulation de signal de fréquence sans fil utilisant une structure à six ports dans un circuit à éléments localisés, l'appareil comprenant : un premier coupleur pour recevoir un signal provenant d'un oscillateur local (LO) et pour émettre celui-ci en tant que deux signaux comportant une différence de phase inversée de façon à obtenir une orthogonalité des deux signaux de sortie ; un second coupleur pour convertir les tailles des signaux divisés par le premier coupleur par ajustement de la charge d'un terminal de sortie ; et un combineur pour ajouter des vecteurs des deux signaux convertis par le second coupleur, et pour délivrer en sortie une fréquence sans fil à un port de sortie, le premier coupleur et le second coupleur étant composés d'une pluralité de condensateurs et d'inducteurs, et les condensateurs étant des condensateurs commutés. La présente invention présente des avantages en ce qu'un appareil de modulation de signal de fréquence sans fil multibande qui utilise un commutateur variable et un coupleur de Lange présente la simplicité structurelle d'une structure à six ports, et consomme donc une petite quantité d'électricité, et en même temps peut être réalisé sous une forme ultra compacte à l'aide d'une puce CI CMOS, et peut être appliqué non seulement dans une bande de fréquence unique mais également dans une bande ultra large. De plus, l'appareil de modulation de signal de fréquence sans fil proposé peut être utilisé en tant que nouvelle structure de transmission dans un système de communication MIMO multibande de prochaine génération.
PCT/KR2017/001954 2017-01-16 2017-02-22 Appareil de modulation de signal de fréquence sans fil WO2018131748A1 (fr)

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Application Number Priority Date Filing Date Title
KR20170007077 2017-01-16
KR10-2017-0007077 2017-01-16
KR10-2017-0019402 2017-02-13
KR1020170019402A KR102002787B1 (ko) 2017-01-16 2017-02-13 무선주파수 신호 변조 장치

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Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN112117972A (zh) * 2020-08-28 2020-12-22 北京无线电测量研究所 一种正交混频器电路
CN116015327A (zh) * 2022-12-05 2023-04-25 电子科技大学长三角研究院(湖州) 一种信能一体化接收方法、接收机、电路

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20020149431A1 (en) * 1999-09-15 2002-10-17 Seyed-Ali Hajimiri Tunable, distributed, voltage-controlled oscillator
US20040021526A1 (en) * 2002-07-30 2004-02-05 Agency For Defense Development Wideband 180° bit phase shifter
US20070159268A1 (en) * 2003-06-25 2007-07-12 Werlatone, Inc. Multi-section coupler assembly
US20100137024A1 (en) * 2007-04-13 2010-06-03 Thingmagic, Inc. Multi-Mode Radio Frequency Communications
US20110009084A1 (en) * 2009-07-10 2011-01-13 Ioannis Papananos Passive high frequency image reject mixer

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20020149431A1 (en) * 1999-09-15 2002-10-17 Seyed-Ali Hajimiri Tunable, distributed, voltage-controlled oscillator
US20040021526A1 (en) * 2002-07-30 2004-02-05 Agency For Defense Development Wideband 180° bit phase shifter
US20070159268A1 (en) * 2003-06-25 2007-07-12 Werlatone, Inc. Multi-section coupler assembly
US20100137024A1 (en) * 2007-04-13 2010-06-03 Thingmagic, Inc. Multi-Mode Radio Frequency Communications
US20110009084A1 (en) * 2009-07-10 2011-01-13 Ioannis Papananos Passive high frequency image reject mixer

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN112117972A (zh) * 2020-08-28 2020-12-22 北京无线电测量研究所 一种正交混频器电路
CN116015327A (zh) * 2022-12-05 2023-04-25 电子科技大学长三角研究院(湖州) 一种信能一体化接收方法、接收机、电路

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