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WO2017038363A1 - Système de gestion d'énergie - Google Patents

Système de gestion d'énergie Download PDF

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Publication number
WO2017038363A1
WO2017038363A1 PCT/JP2016/072888 JP2016072888W WO2017038363A1 WO 2017038363 A1 WO2017038363 A1 WO 2017038363A1 JP 2016072888 W JP2016072888 W JP 2016072888W WO 2017038363 A1 WO2017038363 A1 WO 2017038363A1
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WO
WIPO (PCT)
Prior art keywords
converter
voltage
chopper
bidirectional
llc resonant
Prior art date
Application number
PCT/JP2016/072888
Other languages
English (en)
Japanese (ja)
Inventor
石倉祐樹
Original Assignee
株式会社村田製作所
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 株式会社村田製作所 filed Critical 株式会社村田製作所
Priority to JP2017537683A priority Critical patent/JP6327403B2/ja
Publication of WO2017038363A1 publication Critical patent/WO2017038363A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for AC mains or AC distribution networks
    • H02J3/28—Arrangements for balancing of the load in a network by storage of energy
    • H02J3/32—Arrangements for balancing of the load in a network by storage of energy using batteries with converting means
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for AC mains or AC distribution networks
    • H02J3/38—Arrangements for parallely feeding a single network by two or more generators, converters or transformers
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/34—Parallel operation in networks using both storage and other DC sources, e.g. providing buffering
    • H02J7/35—Parallel operation in networks using both storage and other DC sources, e.g. providing buffering with light sensitive cells
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode

Definitions

  • the present invention relates to an energy management system that uses electric power generated in a house or a factory.
  • An energy management system for example, a photovoltaic power generation system, charges a secondary battery with generated power from a power generation device or power from a power system (commercial power supply), and generates generated power or secondary battery discharge power in a house.
  • a bidirectional DC-DC converter is generally used to convert a DC voltage charged or discharged from the secondary battery into a predetermined constant voltage.
  • Patent Document 1 discloses a DC-DC converter that converts voltage with high efficiency at a predetermined ratio while insulating.
  • the DC-DC converter described in Patent Document 1 has a configuration in which a first converter of a bidirectional chopper and a second converter of an insulated bidirectional DC-DC converter are connected. And when charging a secondary battery, a DC voltage is insulated with a 2nd converter, a voltage is adjusted with a 1st converter, and a secondary battery is charged. When discharging the secondary battery, the voltage is converted into a predetermined voltage by the first converter and insulated by the second converter.
  • a bidirectional DC-DC converter in an energy management system is connected to a DC voltage bus (HVDC bus).
  • a power generation device, an inverter, and the like are connected to the HVDC bus.
  • the bi-directional DC-DC converter in order to stabilize the output from the inverter, the bi-directional DC-DC converter is controlled to charge and discharge the secondary battery, so that the voltage of the HVDC bus always maintains a predetermined voltage value. You are in control.
  • the second converter (on the side opposite to the connection with the first converter) is connected to the HVDC bus. For this reason, when the voltage of the HVDC bus decreases and the secondary battery is discharged and applied to the HVDC bus, the second converter needs to be driven so that the output voltage approaches the voltage of the HVDC bus. Since the second converter is a current resonance type converter, the voltage conversion ratio is determined by the turns ratio of the transformer under the resonance condition. Therefore, when adjusting the output voltage, the second converter needs to perform PFM control. In this case, the second converter is driven out of the resonance condition, and high-efficiency voltage conversion obtained by driving at the optimum driving frequency cannot always be realized.
  • an object of the present invention is to provide an energy management system capable of simultaneously realizing highly efficient voltage conversion and insulation.
  • the energy management system includes a DC voltage bus, a power generator connected to the DC voltage bus and outputting generated power to the DC voltage bus, and a bidirectional DC- connected to the DC voltage bus.
  • DC converter unit and bi-directional DC-DC converter unit connected to convert input AC voltage into DC voltage, output to DC-DC converter unit, and bi-directional DC-DC converter
  • An inverter that converts a DC voltage input from the unit into an AC voltage, and the bidirectional DC-DC converter unit includes a non-insulated chopper converter having a secondary battery connection unit, the chopper converter, and the inverter.
  • a connection point between the chopper converter and the resonant converter is a front end.
  • the chopper converter transforms a DC voltage input from the connection point and outputs it to the secondary battery connection unit, and also outputs a DC voltage input from the secondary battery connection unit.
  • the resonant converter transforms the DC voltage input from the connection point and outputs to the inverter, and transforms the DC voltage input from the inverter to the connection It outputs to the point.
  • the voltage can be transformed to a predetermined value by the chopper converter, and the inverter side and the DC voltage bus side can be insulated by the resonance converter.
  • the input voltage to the resonant converter can be kept constant even if the power output from the power generator varies. It can be driven with high efficiency. As a result, the energy management system can realize high-efficiency voltage conversion and insulation at the same time.
  • Each of the chopper converter and the resonant converter includes a switching element
  • the energy management system further includes a control unit that performs switching control of the chopper converter and the resonant converter, and the control unit includes both
  • a configuration may be employed in which the chopper converter is soft-started when starting the DC-DC converter unit.
  • the input voltage to the resonant converter (the output voltage of the chopper converter) is lower than the steady state when starting the resonant converter. Can be suppressed. For this reason, it is not necessary to configure a resonant converter with an element having a high breakdown voltage. In addition, the resonant converter does not need to be driven in a region where the drive frequency is greatly deviated from the resonance frequency for the purpose of reducing the voltage conversion ratio in order to suppress the inrush current. High-efficiency driving is possible immediately after startup.
  • the control unit may perform switching control of the resonant converter at a fixed frequency after the bidirectional DC-DC converter unit is activated.
  • This configuration eliminates the need for PFM control of the resonant converter and allows constant control at a highly efficient frequency.
  • the control unit may activate the chopper converter and the resonant converter at the same time.
  • FIG. 1 is a diagram illustrating a configuration of an energy management system according to an embodiment.
  • FIG. 2 is a circuit diagram of the power generator and the bidirectional DC-DC converter.
  • FIG. 3 is a circuit diagram of the inverter.
  • FIG. 4 is a diagram illustrating a time chart of gate signals applied to the chopper converter and the LLC resonant converter.
  • FIG. 5 shows the frequency characteristics of the LLC resonant converter.
  • FIG. 1 is a diagram showing a configuration of an energy management system 1 according to the present embodiment.
  • the energy management system 1 includes an HVDC bus 10, a power generator 20, a bidirectional DC-DC converter 30, and an inverter 40.
  • a power generator 20 and a bidirectional DC-DC converter 30 are connected to the HVDC bus 10.
  • the HVDC bus 10 corresponds to a “DC voltage bus” according to the present invention.
  • the bidirectional DC-DC converter 30 corresponds to a “bidirectional DC-DC converter unit” according to the present invention.
  • the power generation device 20 includes a photovoltaic panel 21 and a PV converter 22.
  • the PV converter 22 outputs the electric power generated by the photovoltaic panel 21 to the HVDC bus 10.
  • the power generation device 20 may be a wind power generation device or a gas power generation device.
  • the bidirectional DC-DC converter 30 includes a chopper converter 31, an LLC resonance converter 32, and a control unit 33. As will be described in detail later, the chopper converter 31 and the LLC resonant converter 32 each have switching elements, and the control unit 33 performs switching control of these switching elements.
  • the chopper converter 31 and the LLC resonant converter 32 are connected in series.
  • the HVDC bus 10 is connected to a connection point between the chopper converter 31 and the LLC resonant converter 32. That is, the chopper converter 31 and the LLC resonant converter 32 are each connected to the HVDC bus 10. Further, the secondary battery B ⁇ b> 1 is connected to the chopper converter 31.
  • An inverter 40 is connected to the LLC resonant converter 32.
  • the chopper converter 31 is a non-insulated bidirectional chopper circuit.
  • the chopper converter 31 transforms (steps up or steps down) the DC voltage input from one side and outputs it from the other side. That is, the chopper converter 31 transforms the voltage input from the secondary battery B ⁇ b> 1 and outputs it to the HVDC bus 10. Thereby, the secondary battery B1 is discharged. Further, the chopper converter 31 transforms the voltage input from the HVDC bus 10 and outputs it to the secondary battery B1. Thereby, the secondary battery B1 is charged.
  • the LLC resonant converter 32 is an insulating bidirectional DC-DC converter.
  • the LLC resonant converter 32 insulates and transforms the DC voltage input from the HVDC bus 10 at a predetermined ratio, and outputs it to the inverter 40.
  • the inverter 40 converts the alternating voltage input from the electric power grid
  • the direct current voltage converted by the inverter 40 is input to the LLC resonant converter 32.
  • the LLC resonant converter 32 insulates and transforms the input DC voltage at a predetermined ratio and outputs it to the HVDC bus 10.
  • the inverter 40 is connected to the power system 101 and the distribution board 102 through the switches S1 and S2.
  • An AC output terminal (AC outlet or the like) (not shown) is connected to the distribution board 102.
  • a load such as a microwave oven, a washing machine, and an air conditioner is connected to the AC output terminal.
  • the inverter 40 converts the DC voltage input from the bidirectional DC-DC converter 30 into an AC voltage and outputs the AC voltage to the power system 101 side. Further, the inverter 40 converts an AC voltage input from the power system 101 side into a DC voltage and outputs the DC voltage to the bidirectional DC-DC converter 30.
  • the energy management system 1 controls the power generator 20 and the bidirectional DC-DC converter 30 so that the voltage of the HVDC bus 10 maintains a predetermined value (for example, 380 V). By stabilizing the voltage of the HVDC bus 10, constant power can be stably output from the inverter 40 to the power system 101 or the distribution board 102 side.
  • a predetermined value for example, 380 V.
  • FIG. 2 is a circuit diagram of the power generator 20 and the bidirectional DC-DC converter 30.
  • FIG. 3 is a circuit diagram of the inverter 40.
  • PV converter 22 as shown in FIG. 2, includes an input terminal 22I 1, 22I 2, and an output terminal 22O 1, 22O 2.
  • the input terminals 22I 1 and 22I 2 are connected to the photovoltaic panel 21.
  • Output 22O 1, 22O 2 is connected to the HVDC bus 10.
  • An input terminal 22I 1, 22I 2, between the output terminal 22O 1, 22O 2, inductor 22L, a diode 22D, a chopper circuit comprising a switching element 22S and the capacitor 22C is connected.
  • the PV converter 22 performs switching control of the switching element 22S so that the output voltages from the output terminals 22O 1 and 22O 2 approach the target value.
  • the output voltage from the output terminals 22O 1 and 22O 2 is also the voltage of the HVDC bus 10. Therefore, this control maintains the voltage of the HVDC bus 10 at a predetermined value.
  • the inverter 40 includes input / output terminals 40IO 1 and 40IO 2 and AC connection terminals U, V, and W.
  • the input / output terminals 40IO 1 and 40IO 2 are connected to the LLC resonant converter 32.
  • the AC connection ends U, V, and W are connected to the power system 101 and the distribution board 102 via the switches S1 and S2.
  • Switch circuits by switching elements 40S 1 , 40S 2 , 40S 3 , 40S 4 , 40S 5 , 40S 6 are connected to the input / output terminals 40IO 1 , 40IO 2 .
  • the connection point of the switching elements 40S 1 and 40S 2 is connected to the AC connection end U via the inductor Lu.
  • the connection point of the switching elements 40S 3 and 40S 4 is connected to the AC connection terminal V via the inductor Lv.
  • the connection point of the switching elements 40S 5 and 40S 6 is connected to the AC connection end W via the inductor Lw.
  • Capacitors Cu, Cv, and Cw are connected between the AC connection terminals U, V, and W and the neutral point, respectively.
  • the chopper converter 31 of the bidirectional DC-DC converter 30 includes input / output terminals 31IO 1 , 31IO 2 , 31IO 3 and 31IO 4 .
  • a secondary battery B1 is connected to the input / output terminals 31IO 1 and 31IO 2 .
  • the input / output terminals 31IO 1 and 31IO 2 correspond to the “secondary battery connection unit” according to the present invention.
  • the input / output terminals 31IO 3 and 31IO 4 are connected to the LLC resonant converter 32 and the HVDC bus 10.
  • a non-insulated bidirectional chopper circuit is connected between the input / output terminals 31IO 1 and 31IO 2 and the input / output terminals 31IO 3 and 31IO 4 .
  • This bidirectional chopper circuit includes an inductor 31L, switching elements 31S 1 and 31S 2 and a capacitor 31C.
  • the switching elements 31S 1 and 31S 2 are, for example, n-type MOS-FETs, and their gates are connected to the control unit 33. And a gate signal is applied by the control part 33, and it turns on and off.
  • the LLC resonant converter 32 of the bidirectional DC-DC converter 30 includes input / output terminals 32IO 1 , 32IO 2 , 32IO 3 , 32IO 4 .
  • the input / output terminals 32IO 1 and 32IO 2 are connected to the input / output terminals 31IO 3 and 31IO 4 of the chopper converter 31 and the HVDC bus 10.
  • the input / output terminals 32IO 3 and 32IO 4 are connected to the input / output terminals 40IO 1 and 40IO 2 of the inverter 40.
  • a first switch circuit is connected to the input / output terminals 32IO 1 and 32IO 2 .
  • the first switch circuit includes switching elements 32S 1 , 32S 2 , 32S 3 , 32S 4 .
  • the input and output ends 32IO 3, 32IO 4 is a smoothing capacitor 32C 2 and the second switch circuit is connected.
  • the second switch circuit includes switching elements 32S 5 , 32S 6 , 32S 7 , 32S 8 .
  • the switching elements 32S 1 to 32S 8 are, for example, n-type MOS-FETs, and their gates are connected to the control unit 33. And a gate signal is applied by the control part 33, and it turns on and off.
  • the resonance inductor 32L, a resonance capacitor 32C 1 and the transformer T1 is connected.
  • the transformer T1 is shown as an ideal transformer.
  • Resonant inductor 32L and a resonance capacitor 32C 1 constitute the exciting inductance Lm and LLC resonant circuit of the transformer T1.
  • high voltage conversion efficiency can be obtained by bringing the switching frequency of the first switch circuit or the second switch circuit close to the resonance frequency of the LLC resonant circuit. For example, when a DC voltage input from the input / output terminals 32IO 1 and 32IO 2 is output from the input / output terminals 32IO 3 and 32IO 4 , the switching elements 32S 1 and 32S 4 and the switching elements 32S 2 and 32S 3 are set to 50%. High voltage conversion efficiency can be obtained by turning on and off with a duty and setting the switching frequency to the resonance frequency. The conversion ratio at the time of voltage conversion is determined by the turn ratio between the primary winding and the secondary winding of the transformer T1.
  • the energy management system 1 has a configuration in which the HVDC bus 10 is connected to a connection point between the chopper converter 31 and the LLC resonant converter 32 included in the bidirectional DC-DC converter 30. With this configuration, when the charging voltage of the secondary battery B1 is output from the inverter 40, the energy management system 1 can perform voltage conversion with high efficiency while ensuring insulation between the secondary battery B1 and the inverter 40. This will be specifically described below.
  • the chopper converter 31 transforms the charging voltage of the secondary battery B1 to a predetermined voltage. As described above, the chopper converter 31 is connected to the HVDC bus 10. The voltage of the HVDC bus 10 needs to be maintained at a predetermined value. Therefore, the chopper converter 31 performs switching control of the switching elements 31S 1 and 31S 2 so that the output voltage approaches the target value.
  • the LLC resonant converter 32 transforms the voltage transformed by the chopper converter 31 at a predetermined ratio while ensuring insulation. At this time, the LLC resonant converter 32 performs switching control of the switching elements 32S 1 to 32S 4 at the most efficient switching frequency, that is, the resonant frequency of the LLC resonant circuit.
  • the LLC resonant converter 32 is connected to the HVDC bus 10. In this case, it is necessary to bring the output voltage of the LLC resonant converter 32 close to the target value.
  • the transformation ratio in the LLC resonant converter 32 is determined by the turn ratio of the transformer T1. For this reason, when the output voltage of the LLC resonant converter 32 is brought close to the target value, the LLC resonant converter 32 needs to adjust the output voltage by PFM control. In this case, the LLC resonant converter 32 cannot always be driven with high efficiency.
  • the HVDC bus 10 is configured to be connected to a connection point between the chopper converter 31 and the LLC resonant converter 32.
  • the chopper converter 31 only has to adjust the output voltage, and the LLC resonant converter 32 does not need to adjust the output voltage.
  • the LLC resonant converter 32 can be driven with high efficiency by performing switching control of the switching elements 32S 1 to 32S 4 using the resonant frequency as a switching frequency.
  • the LLC resonant converter 32 can be driven with high efficiency even when the energy management system 1 is activated.
  • FIG. 4 is a diagram showing a time chart of the gate signal applied to the chopper converter 31 and the LLC resonant converter 32.
  • (1) in FIG. 4 is a time chart of the gate signal applied to the switching element 31S 1 of the chopper converter 31.
  • (2) of FIG. 4 is a time chart of the gate signal applied to the switching elements 32S 1 and 32S 4 (or 32S 2 and 32S 3 ) of the LLC resonant converter 32.
  • 4 is a voltage V1 of the HVDC bus 10
  • (4) is an output voltage V2 applied to the inverter 40 from the bidirectional DC-DC converter 30 (output voltages of the input / output terminals 32IO 3 and 32IO 4 ). .
  • the control unit 33 activates the chopper converter 31 and the LLC resonant converter 32 simultaneously. Immediately after startup, the control unit 33 soft-starts the chopper converter 31. As a result, as shown in FIG. 4 (3), the output voltage from the chopper converter 31, that is, the voltage V1 of the HVDC bus 10 rises gently. As a result, the inrush current can be prevented from flowing into the LLC resonant converter 32.
  • the control unit 33 can drive the LLC resonant converter 32 with high efficiency immediately after startup. That is, the control unit 33 sets the resonance frequency to the switching frequency, except for the minimum dead time for preventing the through current from flowing through the switching elements 32S 1 and 32S 4 and the switching elements 32S 2 and 32S 3. ON / OFF at about 50% duty.
  • the control unit 33 soft-starts the chopper converter 31, and when the output voltage of the chopper converter 31 reaches the target value, the control unit 33 ends the soft start and performs PWM control so that the output voltage maintains the target value. Further, the controller 33 continues to drive the LLC resonant converter 32 at the same frequency even after the soft start of the chopper converter 31 is completed.
  • the LLC resonant converter 32 can always be driven with high efficiency immediately after startup. Further, by suppressing the inrush current to the LLC resonance converter 32, each element of the LLC resonance converter 32 does not need to be an element having a high withstand voltage.
  • the rush current to the LLC resonant converter 32 is suppressed by soft-starting the chopper converter 31, but the rush current to the LLC resonant converter 32 by simultaneously starting the chopper converter 31 and the LLC resonant converter 32. Can be further suppressed.
  • the chopper converter 31 is driven first, the LLC resonant converter 32 is driven while the capacitor 31C of the chopper converter 31 is charged. In this case, an inrush current may flow into the LLC resonant converter 32 due to the charging voltage of the capacitor 31C. For this reason, the inrush current can be suppressed by simultaneously starting the chopper converter 31 and the LLC resonant converter 32.
  • the chopper converter 31 and the LLC resonant converter 32 are activated simultaneously. However, after the chopper converter 31 is activated first, the LLC resonant converter 32 is activated during the soft start period of the chopper converter 31. You may do it. Even in this case, since the capacitor 31C is not fully charged, the inrush current can be suppressed.
  • control unit 33 continues to drive the LLC resonant converter 32 at the same frequency both at the start and after the soft start of the chopper converter 31.
  • the LLC resonant converter 32 does not necessarily have to be continuously driven at a fixed frequency.
  • FIG. 5 shows the frequency characteristics of the LLC resonant converter.
  • the horizontal axis is “drive frequency / resonance frequency”, and the vertical axis is “voltage gain (voltage gain)”. Further, in FIG. 5, four types of loads from light loads to heavy loads are graphed as separate curves.
  • Voltage gain means the ratio of the input voltage to the output voltage (output voltage / input voltage).
  • K in FIG. 5 means the minimum value of “voltage gain” at the time of steady operation of the LLC resonant converter (during normal operation after the end of soft start). That is, in this modification, the LLC resonant converter is driven in a predetermined frequency range including the frequency with the highest efficiency during normal operation, and “K” is “voltage gain” in the predetermined frequency range. "Means the minimum value.
  • the LLC resonant converter in order to further suppress the inrush current in the LLC resonant converter, the LLC resonant converter is started to be driven from a frequency at which the voltage gain K is reached during the soft start period of the chopper converter.
  • the drive since the drive is started from the frequency at which the voltage gain K is obtained instead of the frequency at which the efficiency is highest, the inrush current is suppressed while the LLC resonant converter is started to be driven at a relatively high efficiency frequency. can do.
  • the control unit may perform switching control of the LLC resonant converter at a frequency (in the vicinity of the resonant frequency) with higher efficiency.
  • the LLC resonant converter according to the present modification is driven at a frequency that provides a voltage gain of “K” or more at both the soft start period and the normal operation, so that a relatively high-efficiency frequency is achieved.
  • the inrush current is also suppressed while maintaining the drive.
  • B1 Secondary batteries Cu, Cv, Cw ... Capacitor Lm ... Excitation inductances Lu, Lv, Lw ... Inductors S1, S2 ... Switch T1 ... Transformer U, V, W ... AC connection end 1 ... Energy management system 10 ... HVDC bus 20 ... power generator 21 ... photovoltaic panels 22 ... PV converter 22C ... capacitor 22D ... diodes 22I 1, 22I 2 ... inputs 22L ... inductor 22O 1, 22O 2 ... output terminal 22S ... switching device 30 ... DC-DC converter 31 ... chopper converter 31C ... capacitor 31IO 1, 31IO 2, 31IO 3 , 31IO 4 ... output terminal 31L ... inductor 31S 1, 31S 2 ...

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Supply And Distribution Of Alternating Current (AREA)
  • Charge And Discharge Circuits For Batteries Or The Like (AREA)
  • Inverter Devices (AREA)

Abstract

L'invention concerne un système de gestion d'énergie (1) pourvu de : un dispositif de production d'énergie (20) connecté à un bus continu haute tension (HVDC) (10) ; un convertisseur c.c./c.c. bidirectionnel (30) connecté au bus HVDC (10) ; et un onduleur (40) connecté au convertisseur c.c./c.c. bidirectionnel (30). Le convertisseur c.c./c.c. bidirectionnel (30) est configuré en connectant en série un convertisseur hacheur (31) non isolant, et un convertisseur à résonance LLC (32) isolant, et le bus HVDC (10) est connecté à un point de connexion entre le convertisseur hacheur non isolant et le convertisseur à résonance LLC isolant. Le convertisseur hacheur (31) transforme une tension de charge d'une batterie secondaire (B1) en une valeur prédéfinie, et délivre en sortie la tension vers le bus HVDC (10). Le convertisseur à résonance LLC (32) transforme une tension de courant continu entrée à partir du bus HVDC (10), et délivre en sortie la tension vers un onduleur (40). Par conséquent, on obtient le système de gestion d'énergie, qui est susceptible d'obtenir une conversion de tension et une isolation très efficaces simultanées.
PCT/JP2016/072888 2015-09-01 2016-08-04 Système de gestion d'énergie WO2017038363A1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
JP2017537683A JP6327403B2 (ja) 2015-09-01 2016-08-04 エネルギーマネジメントシステム

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
JP2015-171645 2015-09-01
JP2015171645 2015-09-01

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WO2017038363A1 true WO2017038363A1 (fr) 2017-03-09

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WO (1) WO2017038363A1 (fr)

Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2021097465A (ja) * 2019-12-16 2021-06-24 ニチコン株式会社 双方向ｄｃ／ｄｃコンバータ回路および蓄電システム
WO2021149707A1 (fr) * 2020-01-20 2021-07-29 株式会社 東芝 Dispositif de conversion de puissance et dispositif d'alimentation pour sous-station
CN113965064A (zh) * 2020-07-20 2022-01-21 国家能源投资集团有限责任公司 一种隔离型光伏逆变器、方法及光伏并网系统
JP2023123010A (ja) * 2022-02-24 2023-09-05 パナソニックＩｐマネジメント株式会社 充電システム
JPWO2024028947A1 (fr) * 2022-08-01 2024-02-08
EP4358360A1 (fr) * 2022-10-20 2024-04-24 Huawei Digital Power Technologies Co., Ltd. Circuit de distribution d'énergie d'alimentation électrique sans coupure et système d'alimentation électrique

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JP2011239637A (ja) * 2010-05-13 2011-11-24 Harison Toshiba Lighting Corp スイッチング電源装置

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JP2008079480A (ja) * 2006-09-25 2008-04-03 Matsushita Electric Ind Co Ltd 系統連系インバータ装置
US20110090717A1 (en) * 2009-10-21 2011-04-21 Myongji University Industry And Academia Cooperation Foundation Two-stage insulated bidirectional DC/DC power converter using a constant duty ratio LLC resonant converter
JP2011239637A (ja) * 2010-05-13 2011-11-24 Harison Toshiba Lighting Corp スイッチング電源装置

Cited By (13)

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Publication number Priority date Publication date Assignee Title
JP7368218B2 (ja) 2019-12-16 2023-10-24 ニチコン株式会社 双方向ｄｃ／ｄｃコンバータ回路および蓄電システム
JP2021097465A (ja) * 2019-12-16 2021-06-24 ニチコン株式会社 双方向ｄｃ／ｄｃコンバータ回路および蓄電システム
JP7433924B2 (ja) 2020-01-20 2024-02-20 株式会社東芝 電力変換装置および変電所用電源装置
CN114982117A (zh) * 2020-01-20 2022-08-30 株式会社东芝 电力转换装置以及变电站用电源装置
JP2021114854A (ja) * 2020-01-20 2021-08-05 株式会社東芝 電力変換装置および変電所用電源装置
WO2021149707A1 (fr) * 2020-01-20 2021-07-29 株式会社 東芝 Dispositif de conversion de puissance et dispositif d'alimentation pour sous-station
CN113965064A (zh) * 2020-07-20 2022-01-21 国家能源投资集团有限责任公司 一种隔离型光伏逆变器、方法及光伏并网系统
JP2023123010A (ja) * 2022-02-24 2023-09-05 パナソニックＩｐマネジメント株式会社 充電システム
JP7737195B2 (ja) 2022-02-24 2025-09-10 パナソニックオートモーティブシステムズ株式会社 充電システム
JPWO2024028947A1 (fr) * 2022-08-01 2024-02-08
WO2024028947A1 (fr) * 2022-08-01 2024-02-08 三菱電機株式会社 Dispositif d'alimentation électrique pour véhicule ferroviaire
JP7651072B2 (ja) 2022-08-01 2025-03-25 三菱電機株式会社 鉄道車両用の電源装置
EP4358360A1 (fr) * 2022-10-20 2024-04-24 Huawei Digital Power Technologies Co., Ltd. Circuit de distribution d'énergie d'alimentation électrique sans coupure et système d'alimentation électrique

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