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WO2018157797A1 - Convertisseur résonnant en pont complet - Google Patents

Convertisseur résonnant en pont complet Download PDF

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Publication number
WO2018157797A1
WO2018157797A1 PCT/CN2018/077437 CN2018077437W WO2018157797A1 WO 2018157797 A1 WO2018157797 A1 WO 2018157797A1 CN 2018077437 W CN2018077437 W CN 2018077437W WO 2018157797 A1 WO2018157797 A1 WO 2018157797A1
Authority
WO
WIPO (PCT)
Prior art keywords
bridge
full
resonant
switching
rectifying
Prior art date
Application number
PCT/CN2018/077437
Other languages
English (en)
Chinese (zh)
Inventor
王跃斌
崔荣明
宋栋梁
Original Assignee
深圳市皓文电子有限公司
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 深圳市皓文电子有限公司 filed Critical 深圳市皓文电子有限公司
Publication of WO2018157797A1 publication Critical patent/WO2018157797A1/fr

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/4815—Resonant converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02P—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN THE PRODUCTION OR PROCESSING OF GOODS
    • Y02P80/00—Climate change mitigation technologies for sector-wide applications
    • Y02P80/10—Efficient use of energy, e.g. using compressed air or pressurized fluid as energy carrier

Definitions

  • This invention relates to the field of power supplies and, more particularly, to a full bridge resonant converter.
  • the constant frequency phase shift control has become the first choice in the industry due to the simple control mode and parameter design.
  • the problem of constant frequency phase shift control is that the soft switching of the switching tube cannot be realized in a wide input voltage range and a wide load variation range, which affects the efficiency of the converter and causes serious EMI interference. Therefore, in the prior art, the resonant converter generally has the defects that the design method is complicated, the magnetic component is difficult to design, and the soft switch cannot be realized in a large range.
  • the technical problem to be solved by the present invention is that the above-mentioned design method is complicated for the prior art, the magnetic component is difficult to design, and the defect of the soft switch can not be realized in a large range, and the design method is simple and the magnetic component design is relatively easy.
  • the technical solution adopted by the present invention to solve the technical problem thereof is: constructing a full-bridge resonant converter, comprising a full-bridge inverter unit, wherein the full-bridge inverter unit converts an input DC voltage into a square wave, and the square wave sequentially Obtaining an output DC voltage through a resonant network, a high frequency transformer, and a rectifying and filtering unit, and further comprising: a passive switch disposed in the full bridge inverting unit for switching the switching tube of the full bridge inverting unit to zero crossing Auxiliary network.
  • the full bridge inverter unit includes a first half bridge and a second half bridge connected to two DC voltage input ends, and the first half bridge and the second half bridge respectively include two through a switch end serially connected to the switch tube on the DC input voltage terminal;
  • the auxiliary network includes two end points, and the end points are respectively connected with the two switch tubes of the first half bridge and the second half bridge connection.
  • the auxiliary network includes an auxiliary inductor and a DC blocking capacitor; one end of the auxiliary inductor is connected to one end of the DC blocking capacitor, and the other end of the auxiliary inductor and two switches of the first half bridge The connection points of the tubes are connected, and the other end of the DC blocking capacitor is connected to the connection point of the two switching tubes of the second half bridge.
  • the resonant network includes a resonant inductor, a first resonant capacitor, and a second resonant capacitor; the resonant inductor and the first resonant capacitor are serially connected in series to the full bridge inverter unit and the On the signal loop connected to the high frequency transformer winding, the second resonant capacitor is connected in parallel to the primary or secondary winding of the high frequency transformer.
  • one end of the first resonant capacitor is connected to a connection point of two switching tubes of the first half bridge, and the other end thereof is connected to one end of the resonant inductor; the other end of the resonant inductor and the high frequency
  • One end of the primary side of the transformer is connected, and the other end of the primary side is connected to a connection point of two switching tubes of the second half bridge; the second resonant capacitor is connected to the primary side or the secondary side of the high frequency transformer on.
  • the primary side of the high frequency transformer is a winding
  • the secondary side is one or more windings.
  • two switching tubes in a half bridge circuit are respectively controlled by pulse width modulation signals input by their control terminals and each having a 50% duty ratio and having a phase difference of 180 degrees, and two of the one half bridges
  • the control signal is advanced or delayed by a set width at its adjacent high-low level switching timing to form a dead zone of a set width to prevent the two switching tubes from being simultaneously turned on; the two half-bridge circuits are located therein
  • the control signals of the two switching tubes at the top diagonal position have a set phase difference or phase shift angle, and the set phase difference determines the pulse width of the output square wave of the inverter unit.
  • the rectifying and filtering circuit includes a rectifying portion and a filtering portion; the rectifying portion is constituted by a rectifying device, and a connection topology of the rectifying device includes a double current rectification, a full wave rectification form or a full bridge rectification form.
  • the rectifying device is a diode using a common anode or a common cathode current doubler rectifying circuit or a MOSFET using a synchronous rectifying circuit; and the filtering portion is an LC combined filter circuit.
  • the rectifying device is a diode using a common anode or a common cathode rectifying circuit; and the filtering portion thereof is an LC combined filter circuit.
  • a full-bridge resonant converter embodying the present invention has the following beneficial effects: since an auxiliary network is provided in the inverter unit (ie, the switching unit), there is a current in the auxiliary network that varies with the state of the switching device. These currents provide a beneficial supplement to the switching device when it changes state, and the resonant network connected to the output of the switching device cooperates to make the magnetic component of the converter more efficient and simpler in design, while ensuring a wide range of Switching device zero-crossing switching.
  • FIG. 1 is a schematic structural view of an embodiment of a full bridge resonant converter of the present invention
  • Figure 2 is a circuit diagram of a case in the embodiment
  • Figure 3 is a schematic diagram of waveforms in the embodiment
  • Fig. 4 is a schematic structural view of a converter in another case in the embodiment.
  • the full-bridge resonant converter includes a full-bridge inverter unit, and the full-bridge inverter unit inputs an input DC voltage (usually The input power supply is converted into a square wave, and the square wave sequentially passes through the resonant network, the high frequency transformer and the rectifying and filtering unit to obtain an output DC voltage, and further includes being disposed in the full bridge inverter unit (ie, connected in the a passive auxiliary network for switching the switching tube of the full-bridge inverter unit to zero-crossing.
  • the inverter unit of the converter includes four switch tubes, and the four switch tubes are connected together in a full bridge topology to form an inverter unit.
  • the above-described full-bridge inverter unit includes a first half bridge and a second half bridge connected to two DC voltage input ends, and the first half bridge and the second half bridge respectively include two through a switch end serially connected to the switch tube on the DC input voltage terminal;
  • the auxiliary network includes two end points, and the end points are respectively connected with the two switch tubes of the first half bridge and the second half bridge connection. That is to say, in the embodiment, the auxiliary network is connected between the other half bridges in the full bridge inverter unit, and the connection point of each half bridge is the switch end of the two switch tubes of the half bridge.
  • the auxiliary network includes an auxiliary inductor and a DC blocking capacitor; one end of the auxiliary inductor is connected to one end of the DC blocking capacitor, and the other end of the auxiliary inductor is opposite to the first half bridge
  • the connection points of the switch tubes are connected, and the other end of the DC blocking capacitor is connected to the connection point of the two switch tubes of the second half bridge.
  • the resonant network includes a resonant inductor, a first resonant capacitor, and a second resonant capacitor; the resonant inductor and the first resonant capacitor are connected in series and then connected in series to the full-bridge inverter unit The second resonant capacitor is connected in parallel to the winding of the high frequency transformer on the signal loop connected to the high frequency transformer winding.
  • one end of the first resonant capacitor is connected to a connection point of two switching tubes of the first half bridge, and the other end thereof is connected to one end of the resonant inductor; the other end of the resonant inductor and the high frequency
  • One end of the primary side of the transformer is connected, and the other end of the primary side is connected to a connection point of two switching tubes of the second half bridge; the second resonant capacitor is connected to the primary side or the secondary side of the high frequency transformer on.
  • two switching tubes in one half-bridge circuit are respectively controlled by pulse width modulation signals input by their control terminals and each having a 50% duty ratio and having a phase difference of 180 degrees, and
  • the two control signals of the one half bridge are respectively advanced or delayed by a set width at their adjacent high and low level switching timings to form a dead zone of a set width to prevent the two switch tubes from being simultaneously turned on; a set phase difference or phase shift angle between control signals of two switching tubes located at their topological diagonal positions in the two half bridge circuits, the set phase difference determining the square wave output of the inverter unit Pulse width.
  • the primary side of the high frequency transformer is a winding
  • the secondary side is one or more windings.
  • the second resonant capacitor can be connected to the primary winding of the high frequency transformer or to the secondary winding of the high frequency transformer.
  • the second resonant capacitor is connected to the primary winding of the high-frequency transformer. Referring to FIG. 2, in FIG. 2, the second resonant capacitor is connected to the primary winding of the high-frequency transformer. of.
  • FIG. 4 is a schematic structural view of the converter in one embodiment in the present embodiment.
  • the second resonant capacitor of the resonant network is connected to the secondary winding of the high frequency transformer.
  • Fig. 2 shows a specific circuit diagram of the full bridge resonant converter in one case in this embodiment.
  • the second resonant capacitor in Figure 2 is connected in parallel to the primary winding of the high frequency transformer.
  • the inverter unit includes switch tubes S1, S2, S3, and S4 and their accessory components
  • the auxiliary network includes an auxiliary inductor L a and a DC blocking capacitor C g
  • the resonant network includes a resonant inductor L r
  • the rectifying and filtering unit comprises a diode D1, a diode D2, an inductor L f1 , an inductor L f2 , and a capacitor C f
  • the T1 is a high frequency transformer.
  • the inverter unit includes a first half bridge circuit composed of a first switch tube S1 and a second switch tube S2, and a second half bridge circuit composed of a third switch tube S3 and a fourth switch tube S4;
  • One end of the input is sequentially connected to the two switch ends of the first switch tube S1 and the third switch tube S3 and the two switch ends of the second switch tube S2 and the fourth switch tube S4 to the other end of the DC input; in other words
  • the two half bridges are connected in parallel at both ends of the DC input; in the half bridge circuit, the two switch tubes are respectively controlled by pulse width modulation control signals input by the control terminals thereof and each having a 50% duty ratio and a phase difference of 180 degrees
  • the two half-bridge circuits are combined to form a full-bridge circuit having a set phase difference or phase shift angle between control signals of the two switching tubes at the diagonal position of the topology of the full-bridge circuit.
  • the phase difference determines a pulse width of the output square wave of the inverter unit; adjusting the phase difference or the phase shift angle can adjust a DC level of the output of the DC/DC full-bridge resonant converter; the two arms of the inverter unit Switching tube drive signal PWM1, PWM2, PWM3, PWM4 and the output inverter voltage waveform V AB and the current waveforms i r , i La flowing through the resonance network and the auxiliary network are as shown in FIG. 3 .
  • the auxiliary inductance L a of the auxiliary network unit and the DC blocking capacitor C g are obtained after the series connection, and the two ends are respectively connected with the common connection end of the first switching tube S1 and the second switching tube S2 of the first inverter half bridge. It is connected to the common connection end of the third switch tube S3 and the fourth switch tube S4 of the second inverter half bridge. As shown in FIG.
  • the auxiliary network When the second switch S2 and the third switch S3 are turned on, that is, during the [ t 3 - t 4 ] time period, the auxiliary network is connected in parallel with the input source, and the current i La in the auxiliary network is linearly reduced; When the second switch S2 and the fourth switch S4 are turned on, that is, during the [ t 4 - t 5 ] time period, the auxiliary network is disconnected from the input source, and the current i La in the auxiliary network is constant at this time.
  • an auxiliary network added between the first inverter half bridge and the second inverter half bridge interacts with the resonant network during operation, so that the resonant network
  • the performance improvement of the converter in which it is located is further improved.
  • the inductive component in the impedance network of the rear stage of the full bridge circuit is increased, so that the current phase flowing through the primary switching tube lags behind in the actual working process.
  • the full bridge circuit output voltage phase ensures zero-crossing switching of the switching device over a larger range of the converter. In this way, not only the consistency of the performance of the converter over a large range is ensured, but also the use range is wide, and at the same time, the complexity of the converter circuit or the magnetic circuit parameter design is also reduced to some extent. .
  • the resonant network obtains the square wave voltage output from the inverter unit from the connection point of the first switch tube S1 and the second switch tube S2, and the connection point between the third switch tube S3 and the fourth switch tube S4.
  • Figure 3 shows the v AB voltage waveform.
  • the resonant network extracts the fundamental component of the square wave voltage, transmits it to the high-frequency transformer for electrical isolation, and performs rectification and filtering by the rectifying and filtering unit to transmit to the load.
  • the rectifying and filtering circuit includes a rectifying portion and a filtering portion; the rectifying portion is composed of rectifying devices, and the rectifying devices may be connected together by using various topologies to complete rectification, for example, current doubler rectification, Topological connection form for full wave rectification or full bridge rectification.
  • the rectifying device may be a diode using a common anode or a common cathode current doubler rectifier circuit or a MOSFET using a synchronous rectification circuit; the filtering portion is an LC combined filter circuit.
  • the rectifying device may be a diode using a common anode or a common cathode rectifying circuit; the filtering portion is an LC combined filter circuit.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Rectifiers (AREA)

Abstract

La présente invention concerne un convertisseur résonnant en pont complet qui comprend une unité d'onduleur en pont complet, un réseau résonnant, un transformateur haute fréquence, et une unité de redressement et de filtrage. L'unité d'onduleur en pont complet convertit une tension continue entrée en une onde carrée, et l'onde carrée passe de manière séquentielle à travers le réseau résonnant, le transformateur haute fréquence et l'unité de redressement et de filtrage, de telle sorte qu'une tension continue produite est obtenue. Le convertisseur comprend également un réseau auxiliaire passif disposé dans l'unité d'onduleur en pont complet et utilisé pour la commutation de passage par zéro d'un transistor de commutation de l'unité d'onduleur en pont complet. Les composants magnétiques du convertisseur présentent des taux d'utilisation plus élevés et des conceptions simples, de telle sorte que la commutation de passage par zéro de composants de commutation dans une large plage est assurée.
PCT/CN2018/077437 2017-02-28 2018-02-27 Convertisseur résonnant en pont complet WO2018157797A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CN201710113084.3 2017-02-28
CN201710113084.3A CN106787912A (zh) 2017-02-28 2017-02-28 一种全桥谐振变换器

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WO2018157797A1 true WO2018157797A1 (fr) 2018-09-07

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WO (1) WO2018157797A1 (fr)

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106787912A (zh) * 2017-02-28 2017-05-31 深圳市皓文电子有限公司 一种全桥谐振变换器
CN108419349A (zh) * 2018-02-07 2018-08-17 福建睿能科技股份有限公司 低电磁干扰的全桥高频驱动电路、电子镇流器和照明设备
TWI743652B (zh) * 2020-01-09 2021-10-21 呂錦山 具新型ｔｔ控制之零電壓電力逆變電路
CN114123828B (zh) * 2020-08-28 2024-10-29 苏州捷芯威半导体有限公司 逆变电路及调制方法

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CN101488715A (zh) * 2009-02-19 2009-07-22 普天信息技术研究院有限公司 一种dc/dc谐振变换器
CN101771350A (zh) * 2010-02-04 2010-07-07 南京航空航天大学 一种基于t型辅助网络零电压开关全桥直流变换器
CN106787912A (zh) * 2017-02-28 2017-05-31 深圳市皓文电子有限公司 一种全桥谐振变换器
CN206602458U (zh) * 2017-02-28 2017-10-31 深圳市皓文电子有限公司 一种全桥谐振变换器

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US5132889A (en) * 1991-05-15 1992-07-21 Ibm Corporation Resonant-transition DC-to-DC converter
CN101488715A (zh) * 2009-02-19 2009-07-22 普天信息技术研究院有限公司 一种dc/dc谐振变换器
CN101771350A (zh) * 2010-02-04 2010-07-07 南京航空航天大学 一种基于t型辅助网络零电压开关全桥直流变换器
CN106787912A (zh) * 2017-02-28 2017-05-31 深圳市皓文电子有限公司 一种全桥谐振变换器
CN206602458U (zh) * 2017-02-28 2017-10-31 深圳市皓文电子有限公司 一种全桥谐振变换器

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